International Journal of Antennas and Propagation

Volume 2012 (2012), Article ID 531436, 6 pages

doi:10.1155/2012/531436

Research Article

Hybrid Dielectric Resonator Antenna Composed of High-Permittivity Dielectric Resonator for Wireless Communications in WLAN and WiMAX

Yih-Chien Chen

Department of Electrical Engineering, Lunghwa University of Science and Technology, Shiang, Taoyuan County, 33306 Gueishan, Taiwan

Received 26 January 2012; Accepted 22 May 2012

Academic Editor: Dalia N. Elshiekh

Copyright © 2012 Yih-Chien Chen. This is an open access article distributed under the Creative Commons Attribution License, which permits unrestricted use, distribution, and reproduction in any medium, provided the original work is properly cited.

Abstract.

The-hybrid dielectric resonator antenna consisted of a cylindrical high-permittivity dielectric resonator, a rectangular slot, and two-rectangular patches were implemented. The hybrid dielectric resonator antenna had three resonant frequencies. The lower, middle, and higher resonant frequencies were associated with the rectangular slot, rectangular patches, and dielectric resonator, respectively. Parametric investigation was carried out using simulation software. The proposed hybrid dielectric resonator antenna had good agreement between the simulation results and the measurement results. The hybrid dielectric resonator antenna was implemented successfully for application in 2.4/5.2/5.8 GHz of WLAN and 2.5/3.5/5.5 GHz of WiMAX simultaneously.

1. Introduction

Many commercial applications, including mobile radio and wireless communications, use microstrip antennas. However, these microstrip antennas have a limited range of sizes, bandwidth, and efficiency. On the other hand, dielectric resonator (DR) antenna is attractive due to its small-size, high-radiation efficient, and ease of excitation [1, 2]. Many investigations of DR antenna composed of DR with relatively small permittivity around 10 have examined to enhance radiation capability [3–5]. Many works have focused on using DR with high-permittivity to promote device miniaturization when DR antenna operated at low frequency. However, these antennas composed of high-permittivity DR had a small bandwidth [6].

The use of dual band antennas in WLAN (wireless local area network) has been increasing rapidly in the last decade. Dual band antennas applied in ISM (Industrial, Scientific, Medical, 2.4–2.484 GHz) in low band of WLAN. At the same time, dual band antennas also applied in high band of WLAN, including HIPERLAN (high-performance radio local area network, 5.15–5.35 GHz), and UNII (unlicensed national information infrastructure, 5.725–5.825 GHz). Dual band DR antennas were implemented by placing a parasitic element near the radiation part [7], or stacking many DR [8]. On the other hand, associating with the rapid development of WiMAX (worldwide interoperability for microwave access, 2.5–2.69, 3.3–3.8, and 5.25–5.85 GHz), there is an increasing demand for antennas suitable for WLAN/WiMAX simultaneously. In this paper, the hybrid DR antenna, consisting of a cylindrical high-permittivity dielectric resonator, a rectangular slot, and two-rectangular patches, operated in the ISM, HIPERLAN, UNII, and WiMAX bands simultaneously. Multiband hybrid DR antenna was implemented. However, the volume of hybrid DR antenna did not increase. The radiating resonators in the hybrid DR antenna were assembled tightly and resonated at three frequencies. The characteristics of hybrid DR antenna, such as return loss, radiation pattern, and gain were measured and discussed.

2. Design and Measurement

The resonant frequency of the cylindrical DR antenna excited at the dominant TM₁₁₀ mode is [1]

where is the first zero of the equation , and c is the speed of light in a vacuum. The parameters of r, h, and is the radius, height, and permittivity of the DR, respectively. Figure 1 shows the configuration of the proposed hybrid DR antenna, consisting of a rectangular slot, a cylindrical high-permittivity DR, and two-rectangular patches.The rectangular RF4 substrate had dimensions of  mm² and thickness of 1.6 mm. The cylindrical DR was fed with microstrip line. The microstrip feed line was placed below the centerline (x-axis in the figure) of the DR. Dimensions of the microstrip feed line on FR4 substrate was calculated by close-form formulas given in [9], assuming infinite ground plane and finite dielectric thickness. The microstrip feeding line had length of 28.0 mm and width of of 3.0 mm. The DR had a high-permittivity , radius  mm, and height  mm. The DR was a low-loss ceramic system composed of La and . The rectangular slot on the back side of the FR4 substrate fed with microstrip line, resonated at approximately half-guided wavelength, , where was the guided wavelength of the slot. The length of rectangular slot was 31 mm. Adjusted the length of the rectangular slot adjusted the lower resonance frequency. Adjusting the width of the rectangular slot enabled impedance matching. The bandwidth at lower resonant frequency could be adjusted by adjusting the width of the rectangular slot. The rectangular patches were placed at the two sides of microstrip feed line. The electric field distributions along the top and bottom edges of the rectangular patches were in-phase, and hence these edges were referred to as radiating edges. The electric field distributions in the right and left edges of the rectangular patches were out of phase, and hence these edges were referred to as nonradiating edges (NREs) [10]. The rectangular patches were designed at a resonant frequency of 3.5 GHz. The lengths of the rectangular patches were designed to be /2, where was the guided wavelength of the rectangular patch [11]. The middle resonance frequency could be adjusted by adjusting the length of the rectangular patches. Impedance matching could be realized by adjusting the width of the rectangular patch. Therefore, the bandwidth at middle frequency could be adjusted by adjusting the width of the rectangular patch. In simulation, the conducting grounds and the substrates were assumed to be finite in transverse plane. Reflection coefficient was measured on a PNA-L network analyzer (N5230A). Radiation patterns were measured in a chamber. A standard-double-ridged horn antenna was used as a transmitting antenna. The hybrid DR antenna was mounted on a position which was controlled by a computer.

Figure 1: Configuration of hybrid DR antenna consisted of a rectangular slot, a cylindrical high-permittivity DR, and two-rectangular parasitic patches.

3. Parametric Study

Figures 2 and 3 show the simulation return loss of the hybrid DR antenna with different DR height and DR permittivity, respectively. From the results, the upper resonant frequency decreased from 5.70 to 5.55 GHz as DR height increased from 2 to 4 mm. This phenomenon can be explained by using (1). The larger the DR height enabled the lower the resonant frequency of DR antenna. The upper resonant frequency decreased from 5.74 to 5.55 GHz as DR permittivity increased from 15 to 30. As shown in (1), the larger the DR permittivity enabled the lower the resonant frequency of DR antenna. The upper resonant frequency of hybrid DR antenna was demonstrated to be dominated by the DR parameters. The middle resonant frequency nearly unchanged as DR parameters varied. Additionally, the lower resonant frequency was slightly affected by the DR parameters. The variation in low resonant frequency may have been caused by the resonant length of rectangular slot was approximately half-guided wavelength. A higher the DR height and a larger the DR permittivity, is associated with a larger effective permittivity and, therefore, a lower resonant frequency.

Figure 2: Simulation return loss of hybrid DR antenna with different DR height.

Figure 3: Simulation return loss of hybrid DR antenna with different DR permittivity.

Figures 4 and 5 show the simulation return loss of the hybrid antenna with different length and width of rectangular patch, respectively. The middle resonant frequency decreased from 3.95 to 3.80 GHz as the length of rectangular patch increased from 18 to 20 mm. Since the resonant length of rectangular patch was half-guided wavelength, the longer the length of rectangular patch enabled the lower the resonant frequency. The influence of the width of rectangular patch on the middle resonant frequency was not evident compared with that of the influence of the length of rectangular patch. The higher resonant frequency decreased as the rectangular patch length and width increased. By increasing the rectangular patch length and width, the effective permittivity of the hybrid DR antenna increased. This leaded to reduce the resonant frequency of the DR antenna.

Figure 4: Simulation return loss of hybrid antenna with different rectangular patch length.

Figure 5: Simulation return loss of hybrid DR antenna with different rectangular patch width.

Figures 6 and 7 present the simulation return loss of the hybrid DR antenna with different length and width of rectangular slot, respectively. The lower resonant frequency decreased from 2.70 to 2.55 GHz as the length of rectangular slot increased from 29 to 31 mm. This was because of the resonant length of rectangular slot was half-guided wavelength. The longer the length of rectangular slot enabled the lower the resonant frequency. The higher resonant frequency of the hybrid DR antenna decreased slightly as the length of rectangular slot increased. This was associated with the effective height of DR increased as the length of rectangular slot increased. The influence of the width of rectangular slot on the resonant frequency was slight. The return loss reduced in the lower and middle resonant frequencies as the width of rectangular slot increased. On the contrary, the return loss increased in the higher band as the width of rectangular slot increased.

Figure 6: Simulation return loss of hybrid DR antenna with different rectangular slot length.

Figure 7: Simulation return loss of hybrid DR antenna with different rectangular slot width.

4. Results and Discussion

Figure 8 shows the measurement and simulation return loss of the hybrid DR antenna. The measurement resonant frequency was close to the simulation resonant frequency. The lower, middle, and higher resonant frequencies were associated with the rectangular slot, the rectangular patches, and DR, respectively. The return losses were , , and  dB at 2.36, 3.88, and 5.66 GHz, respectively. There was a 10 dB return loss bandwidth of 1789 MHz (2273–4062 MHz) and 791 MHz (5127–5918 MHz). Alternatively, the antenna had a 10 dB bandwidth of 56% and 14%, which covered the required bandwidth 2400–2484 MHz, 2500–2690 MHz, 3300–3800 MHz, 5150–5350 MHz, 5250–5850 MHz, and 5725–5825 MHz, simultaneously. The bandwidth was enough for many practical applications. The bandwidth at the higher resonant frequency, associating with the cylindrical DR with high-permittivity, was larger than the typical value of 6 ~12% of conventional DR antenna using DR with permittivity around 10 [2–5].

Figure 8: Measurement and simulation return loss of hybrid DR antenna.

Figure 9 displays the radiation patterns of the hybrid DR antenna in the xz-plane and yz-plane at resonant frequencies of 2.36 GHz, 3.88 GHz, and 5.66 GHz. The radiation patterns were stable across the return  dB bands. The radiation patterns were almost omnidirectional in the xz-plane at resonant frequencies of 2.36 and 3.88 GHz. The radiation patterns in the yz-plane at resonant frequencies of 2.36 GHz, 3.88 GHz, and 5.66 GHz were symmetrical about the broadside direction and rolled-off as the elevation angle increased from broadside until about 90°. The cross-polarized patterns were about 15 dB less than the co-polarized patterns in the broadside direction () at 2.36 and 3.88 GHz. Radiation patterns at 2.36 GHz and 3.88 GHz were similar to conventional rectangular slot antenna and rectangular patch antenna, respectively. The radiation patterns at 5.66 GHz on the DR side were similar to those of the conventional DR antenna [12, 13], and the difference on the substrate side was associated with backlobe radiation from the slot. Large cross-polarization was observed at 5.66 GHz. However, large cross-polarization became an advantage for practical applications. The wave propagated with multiple reflections between the transmitter and receiver in indoor applications.

(a)

(b)

(c)

(d)

(e)

(f)

Figure 9: Radiation patterns of hybrid DR antenna at resonant frequency of (a) 2.36 GHz in the xz-plane, (b) 2.36 GHz in the yz-plane (c) 3.88 GHz in the xz-plane, (d) 3.88 GHz in the yz-plane, (e) 5.66 GHz in the xz-plane, and (f) 5.66 GHz in the yz-plane.

Figures 10 and 11 display the gain of the proposed antenna for operating frequencies from 2.4 to 2.9 GHz and from 3.3 to 5.9 GHz, respectively. The peak gains were about 0.5, , and 1.9 dBi in the ISM, HIPERLAN, and UNII bands, respectively. The gain variations were 1.4, 1.6, and 0.4 dBi for frequencies within the ISM, HIPERLAN, and UNII bands, respectively. The peak gains were about 1.9 and 2.0 dBi in the 3.5 and 5.5 GHz WiMAX bands, respectively. The gain variations were 4.0 and 3.9 dBi for frequencies within the 3.5 and 5.5 GHz WiMAX bands, respectively.

Figure 10: Measured gains of hybrid DR antenna for operating frequencies from 2.4 to 2.9 GHz.

Figure 11: Measured gains of hybrid DR antenna gain for operating frequencies from 3.3 to 5.9 GHz.

Acknowledgment

This work was supported by the National Science Council in Taiwan under Grant no NSC 100-2622-E-262-007-.

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