International Journal of Antennas and Propagation

Volume 2014 (2014), Article ID 797930, 7 pages

http://dx.doi.org/10.1155/2014/797930

Research Article

Triband Omnidirectional Circularly Polarized Dielectric Resonator Antenna with Top-Loaded Alford Loop

Chunxia Cheng, Fushun Zhang, Yali Yao, and Fan Zhang

National Laboratory of Science and Technology on Antennas and Microwaves, Xidian University, Xi’an 710071, China

Received 22 May 2014; Revised 12 August 2014; Accepted 17 August 2014; Published 1 September 2014

Academic Editor: Byungje Lee

Copyright © 2014 Chunxia Cheng et al. This is an open access article distributed under the Creative Commons Attribution License, which permits unrestricted use, distribution, and reproduction in any medium, provided the original work is properly cited.

Abstract.

A triband omnidirectional circularly polarized dielectric resonator antenna with a top-loaded modified Alford loop for GSM, WLAN, and WiMAX applications is proposed. Fed by an axial probe, the DRA (dielectric resonator antenna) radiates like a vertically polarized electric monopole. The top-loaded modified Alford loop provides an equivalent horizontally polarized magnetic dipole mode at triband. Omnidirectional CP (circular polarized) fields can be obtained when the two orthogonally polarized fields are equal in amplitude with phase quadrature. The antenna has been successfully simulated, fabricated, and measured. The experimental and numerical results exhibit that the antenna can obtain usable CP bandwidths of 1.925–1.955 GHz, 2.36–2.48 GHz, and 3.502–3.53 GHz with return loss larger than 10 dB and axial ratio less than 3 dB. In addition, over the three bands, the antenna obtains very good omnidirectional CP radiation patterns in the azimuth plane. Moreover, an average CP gain in the azimuth plane of 1.2, 1.6, and −1.5 dBic for the lower, middle, and upper bands has been obtained.

1. Introduction

In modern wireless communication systems, the demand for antennas with multiband operations has increased since such antennas are vital for combining multiple different communication standards in a single compact wireless system. Also, circularly polarized antennas are widely used in modern wireless systems to suppress multipath interferences. Moreover, omnidirectional antennas are very attractive for applications in wireless communications because they can provide full coverage of signal to maintain good communication links at all angles. Thus, multiband omnidirectional circular polarized antennas are ideal for modern wireless communications. Several types of triband antennas have been reported, such as a CPW-fed monopole antenna with a parasitic circular patch and a pair of symmetrical inverted- strips in [1], a monopole antenna with complementary split-ring resonators in [2], a single-loop resonator in [3], and a rectangle-loaded monopole antenna with inverted- slot in [4]. However, those designs can only provide triband linear-polarized omnidirectional patterns. As the growing interest in multiband CP antennas, various designs of multiband circularly polarized antennas have also been proposed, including the dual-band CPW-fed circularly polarized antenna with two orthogonal slots [5], a dual-band CP antenna with two square slots in the opposite corner of the ground plane and two truncated corners of the main slot [6], and a dual-band circularly polarized antenna with slots loaded in the two opposite corners and the halberd-shaped strip connected at the end of the signal line [7]. Unfortunately, although the above designs achieve multiband CP radiations, they all cannot achieve omnidirectional patterns. In addition, several types of omnidirectional CP antennas with single-band [8, 9] or dual-band [10] have been found in recent literatures. However, those designs can only provide one or dual operation band.

In this paper, a triband omnidirectional CP cylindrical dielectric resonator antenna (DRA) with a top-loaded modified Alford loop which satisfies 1.9 GHz GSM, 2.4 GHz WLAN, and 3.5 GHz WiMAX applications is proposed. The DRA radiates like an electric monopole and the top-loaded modified Alford loop radiates as an equivalent magnetic dipole. By properly selecting shapes and dimensions of the DRA and the Alford loop, the orthogonal electric fields of the equivalent electric and magnetic dipoles which are equal in amplitude with phase quadrature within the three separate frequency bands can be achieved. Details of the antenna design and experimental results are presented and discussed.

2. Antenna Design

The antenna design presented here is based on the omnidirectional circularly polarized dielectric resonator antenna with top-loaded Alford loop in [9]. In the present work, by modifying the top-loaded Alford loop the two orthogonally polarized fields are equal in amplitude with phase quadrature in three bands. The configuration of the proposed triband omnidirectional CP cylindrical DRA is shown in Figure 1. The DRA is designed to resonate in the middle band (about 2.4 GHz) with a diameter of  mm, a height of  mm, and a dielectric constant of . The resonant frequency of the DRA in TM01δ-mode can be estimated using [11]:

The proposed DRA can be matched easily by simply adjusting the length of the probe. It is found that a good match can be obtained when  mm. As shown in Figure 1(a), the circular patch of the modified Alford loop that locates on the top of the DRA has a diameter of . Four conducting curved branches with the same width are extended from the patch and oriented in the counterclockwise direction. Four conducting curved branches with gradually narrow width are extended from the outer of the four inner branches. By adjusting the sizes of the modified Alford loop and ground plane (), the radiation fields of the electric and magnetic monopoles can be made equal in amplitude with phase quadrature, which are required for generating CP fields. The detailed dimensions of the proposed circularly polarized antenna are listed in Table 1. The lengths of the branches are approximately determined by

where is a quarter of the circular patch circumference, is the length of the inner branch, is the average length of the outer branch, is the distance between the inner branch and the circular patch, and is the distance between the outer branch and the circular patch. , , and are the lower, middle, and upper wave length, respectively. They are given by

where , , and are the lower, middle, and upper resonant frequency and is the relative effective permittivity.

Table 1: Dimensions of the proposed antenna (unit: mm).

50
22.5
47
10
1.27
29.7
7.4
10.8
11.8
14.6
1.4
1.3
1.2
3.1

(a)

(b)

Figure 1: Configuration of the proposed antenna. (a) Top view. (b) Side view.

For clarifying the improvement process, three prototypes of the antenna are defined as follows (Figure 2): Ant. I is the original antenna with four conducting curved branches of the same width extended from the top-loaded patch; Ant. II has four conducting curved branches with the same width which are extended from the outer of Ant. I; Ant. III is the final construction with the gradually narrow outer branches modified from those of Ant. II. These three prototypes are simulated by a high frequency structure simulator (HFSS 13.0) and the detailed performances are presented in Figure 3: Ant. I has one usable circularly polarized band (overlap bands of return loss > 10 dB and AR < 3 dB), while Ant. II and Ant. III have three. Furthermore, the useable bandwidths of Ant. III are broader, especially the middle band. It is observed that the gradually narrow outer branches have positive influence on circular polarized fields of the antenna.

(a)

(b)

(c)

Figure 2: Three prototypes of the antenna. (a) Ant. I, (b) Ant. II, and (c) Ant. III.

(a)

(b)

(c)

Figure 3: Simulated return loss and axial ratio (theta = 90 deg and phi = 0 deg) of various antennas involved. (a) Ant. I, (b) Ant. II, and (c) Ant. III.

The resonant E fields of xoy-plane inside the DRA for the lower (1.937 GHz), middle (2.45 GHz), and upper (3.51 GHz) frequencies of 0 deg, 90 deg, 180 deg, and 270 deg are simulated using HFSS. The simulated fields are shown in Figure 4. In the three frequencies, the wave propagation direction is along the outer normal direction of the DRA. In order to determine the wave polarization, we observed electric field vector direction (inside the black dotted line) variety with phase angles. In the lower frequency, the observed E field flows from the -axis and -axis to -axis, and the wave propagation direction is -axis, generating a RHCP radiation. In the middle frequency, the observed E field flows from the -axis and -axis to -axis, resulting in a LHCP. And in the upper frequency, the observed E field flows from the -axis and -axis to -axis, also producing a LHCP.

(a)

(b)

(c)

(d)

Figure 4: Simulated E fields inside the DRA at the three resonant frequencies with four phase angles: (a) 0°, (b) 90°, (c) 180°, and (d) 270°.

3. Experimental Results and Discussion

According to the dimensions shown in Figure 1, a fabricated prototype for the proposed antenna has been constructed and measured. The photograph of the prototype is exhibited in Figure 5. The simulated and measured return loss and axial ratio (theta = 90 deg and phi = 0 deg) versus frequency are shown in Figure 6. The measured 10 dB impedance bandwidths are 35 MHz (1.92–1.955 GHz), 185 MHz (2.315–2.50 GHz), and 135 MHz (3.415–3.55 GHz), respectively, and the 3 dB axial ratio bandwidths are approximately 70 MHz (1.925–1.985 GHz), 120 MHz (2.36–2.48 GHz), and 28 MHz (3.502–3.53 GHz). It is observed that the usable bandwidths are 30 MHz (1.925–1.955 GHz), 120 MHz (2.36–2.48 GHz), and 28 MHz (3.502–3.53 GHz). There has been a good agreement between the simulated and measured results.

Figure 5: Photograph of the proposed antenna.

(a)

(b)

(c)

Figure 6: Simulated and measured return loss and AR of the proposed antenna. (a) Lower band, (b) middle band, and (c) upper band.

The RHCP and LHCP radiation patterns are measured in the azimuth (x-y plane) and elevation (x-z plane) planes at the frequency of 1.937, 2.45, and 3.51 GHz in Figure 7. It is seen that the proposed antenna exhibits a good omnidirectional CP pattern in the azimuth plane and a bidirectional pattern in the elevation plane.

(a)

(b)

(c)

Figure 7: Simulated and measured radiation patterns in the azimuth plane (left) and the elevation plane (right). (a) 1.937 GHz. (b) 2.45 GHz. (c) 3.51 GHz.

The measured CP gains in the -plane of the proposed antenna are shown in Figure 8. From the right figure of Figure 7, it can be seen that the maximum CP gain for the upper band is not in the -plane, but the maximum CP gains for the lower and middle bands are in the -plane. The ground plane is larger relative to the upper frequency wavelength; thus the maximum CP gain is above -plane. So, the CP gain for upper bands is low. The average gains of 1.2, 1.6, and −1.5 dBic for the lower, middle, and upper bands, respectively, are obtained.

Figure 8: Measured CP gains against frequency for the proposed antenna.

4. Conclusion

In this paper, a triband omnidirectional CP DRA with a top-loaded modified Alford loop is proposed. The DRA fed by an axial probe at the center of its bottom. The technique of combining equivalent electric and magnetic monopoles is adopted in the design; the former and the latter are obtained through the DRA and the modified Alford loop, respectively. By tuning the dimensions of the Alford loop, the radiation fields of the equivalent electric and magnetic monopoles can be made equal in amplitude but different in phase by 90° at three resonant frequency bands, thus generating triband omnidirectional CP fields. The usable bandwidths of the antenna are 1.5%, 5.0%, and 1.0%. In addition, the antenna shows good omnidirectional CP radiation patterns in the azimuth plane over the three bands. And the average CP gains in -plane are 1.2, 1.6, and −1.5 dBic for the lower, middle, and upper bands, respectively.

Conflict of Interests

The authors declare that there is no conflict of interests regarding the publication of this paper.

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