International Journal of Antennas and Propagation
Volume 2016 (2016), Article ID 3976936, 8 pages
http://dx.doi.org/10.1155/2016/3976936

Research Article

Compact Antenna with Frequency Reconfigurability for GPS/LTE/WWAN Mobile Handset Applications

Lingsheng Yang,¹ Biyu Cheng,¹ Yongan Zhu,¹ and Yajie Li²

¹Jiangsu Key Laboratory of Meteorological Observation and Information Processing and Research Center of Applied Electromagnetics of NUIST, Nanjing University of Information Science & Technology, Ningliu Road, Nanjing 210044, China
²Zhongda Hospital, Southeast University, Dingjiaqiao, Nanjing 210009, China

Received 12 September 2016; Revised 8 November 2016; Accepted 22 November 2016

Academic Editor: Paolo Burghignoli

Copyright © 2016 Lingsheng Yang et al. This is an open access article distributed under the Creative Commons Attribution License, which permits unrestricted use, distribution, and reproduction in any medium, provided the original work is properly cited.

Abstract.

A compact frequency reconfigurable antenna for mobile handset application is proposed in this paper. The antenna consists of an inverted L-shaped feeding strip, a shorter grounded strip, and a longer grounded strip which is connected with four inductors by using a single-pole four-throw RF switch. When we change the working states of the RF switch, the corresponding inductor is connected with the long grounded strip and different resonant modes of the antenna can be realized. The measured −6 dB impedance bandwidth of the presented antenna is 683–960 MHz and 1460–2820 MHz, which is able to cover the LTE700/GSM850/900 and GPS/DCS1800/PCS1900/UMTS2100/LTE2300/2500 bands. The antenna gain, radiation efficiency, and radiation patterns are also described in the paper.

1. Introduction

With the rapid development of wireless communication, more and more wireless applications like the Wireless Wide Area Network (WWAN), Long Term Evolution (LTE), and Global Positioning System (GPS) have been developed. The antenna for mobile handset requires the integration of as many applications as possible [1]. However, the space left for antenna is highly constrained, which makes antenna design a challenge task [2–4].

Frequency reconfiguration of antenna is a powerful method for solving this problem [5]. Recently, many kinds of reconfigurable antennas have been reported [6–13]. In [6], the authors use PIN diodes to control the antenna operating modes. The antenna can cover the GSM900 band in PIFA mode and the GSM1800/GSM1900/UMTS bands in loop mode. However, the LTE700 band and LTE2300/2500 bands are not taken into consideration. A folded coupled-fed reconfigurable narrow-frame antenna is presented in [7]. In order to obtain wide bandwidth in the lower band, PIN diode is inserted in the strip to generate different resonant modes; however, the antenna cannot cover the LTE700 band either. A PIFA with a PIN diode for frequency reconfigurable operation is proposed in [8]. The antenna has a simple structure and can cover the LTE700 bands; however, it has a relatively large dimension and does not include the LTE2300/2500 bands.

In order to cover all the LTE/WWAN operation bands (cover a bandwidth of 698–960 MHz and 1710–2690 MHz), many efforts have been made [9–13]. Antenna connected PIN diode with simple geometry and relatively increased size is proposed in [9]. In [10], the authors proposed multimode reconfigurable antennas by changing the bias states of PIN diode to control the coupling between strips and adjust the fundamental resonant frequency, while in [11] six different resonant pathways are obtained by adjusting the bias states of two PIN diodes. With embedded circuit elements and passive reconfigurable technique, triple-wide-band can be realized in [12]. Antenna for LTE/WWAN tablet computer applications can be realized when RF switch is used to change the resonant modes of lower band among different working states [13].

In this paper, a compact frequency reconfigurable antenna is proposed for mobile handset applications. The antenna has a dimension of 12 × 28 mm² which is smaller than most of the previous designs (see some of the comparison in Table 1). Under the −6 dB impedance matching criterion, the proposed antenna has wider bandwidth in both lower and upper gigahertz bands, which means the antenna can integrate more wireless applications simultaneously within a more compact size. Meanwhile, the gain and efficiency performances show the antenna has acceptable performances through the whole GPS, WWAN, and LTE bands.

Table 1: Size and performance of previously reported antennas and the proposed antenna.

Number
Size (mm²)
Efficiency
Gain (dBi)
Achieved bandwidth (MHz)
Relative bandwidth
Reconfigurability cost

[9]
15 × 60
>70%/>60%
2~2.5/4.2~5
698~960/1710~2690
31.6%/44.5%
PIN diode

[11]
10 × 36.5
>52.83%/>52.14%
0.13~1.59/0.68~3.85
698~960/1710~2690
31.6%/44.5%
PIN diode

[13]
12 × 40
>50%/>50%
1~3/2~4
698~960/1710~2690
31.6%/44.5%
RF switch and lumped inductances

Proposed antenna
12 × 28
>50%/>60%
−1.43~2.28/0.42~2.0
683~960/1460~2820
33.7%/63.6%
RF switch and lumped inductances

2. Antenna Design

The proposed antenna is placed on a 0.8 mm thick FR4 dielectric substrate with a permittivity of 4.4 and a loss tangent of 0.02. The flat area of the board is 140 × 70 mm² which stands for a typical 5.5-inch smart phone. As shown in Figure 1, the radiating part of the antenna consists of an inverted L-shaped feeding strip and two coupling fed grounded strips. The inverted L-shaped feeding strip (blue) and the shorter grounded strip (orange and green) are printed on the upper layer of the substrate, while the longer grounded strip (orange and black) is folded with a height of 4 mm upon the substrate after going through a single-pole four-throw RF switch (RF1604). The switch is used to connect the inductors and the longer grounded strip. Detailed size of the proposed antenna is described in Table 2, and the schematic of the RF switch is shown in Figure 2.

Table 2: The parameters of the proposed antenna.

Parameter
Value (mm)

a1
1.5

a2
5

a3
1.5

a4
3

a5
3

a6
1

a7
3.7

a8
2.7

a9
3.7

b1
21.5

b2
4.8

b3
3

b4
28

L1
23.7

L2
14.5

L3
22

1

0.5

0.3

1

c1
4.8

c2
0.8

(a)

(b)

Figure 1: Geometry of the proposed antenna. (a) Detailed dimensions. (b) Overall structure.

Figure 2: RF switch schematic diagram.

The connection states of the four lumped inductors are controlled by the bias voltages on the two ports of the switch as (V1, V2). For one state of the RF switch, only one lumped inductor is connected. The states of the RF switch and the relevant operating bands can be found in Table 3. In the lower band the resonance frequencies decrease with the increase of the inductance. By using frequency reconfiguration, the proposed antenna can cover a lower band of 683–960 MHz and an upper band of 1460–2820 MHz, including LTE700/GSM850/900 and GPS/DCS1800/PCS1900/UMTS2100/LTE2300/2500 bands for mobile phone applications.

Table 3: The states of RF switch and operating bands.

States
V1
V2
Output inductor
Operating bands

1
Low
Low
4.7 nH
792–960 MHz/1485–2820 MHz

2
High
Low
13 nH
749–793 MHz/1460–2720 MHz

3
Low
High
15 nH
717–760 MHz/1480–2680 MHz

4
High
High
18 nH
683–720 MHz/1460–2620 MHz

For the proposed antenna, the inverted L-shaped feeding strip not only couples the energy to the grounded strips but also realizes the first high resonant frequency in the upper band at around 1780 MHz. From Figure 3, it can be observed that increasing the length of the inverted L-shaped strip lowers the first resonance frequency in the upper band. Other resonance frequencies in the upper band are also affected due to the coupling effects between the L-shaped strip and grounded strips.

Figure 3: Reflection coefficient of the proposed antenna for different value of L1.

The shorter grounded strip mainly affects the second resonant frequency in the upper band at about 2040 MHz. Figure 4 shows the reflection coefficients of the proposed antenna with different value of L2. It can be observed that the second high resonance frequency will decrease while L2 becomes longer. When the second high resonance frequency becomes close to the first one, the antenna will achieve a wide impedance matching band.

Figure 4: Reflection coefficient of the proposed antenna for different value of L2.

The longer grounded strip connected with lumped inductors is responsible for the resonant frequencies in the lower band, the third high resonant frequency in the upper band. Meanwhile, the coupling with shorter grounded strip will also have a certain effect on the second high resonant frequency. Taking the case of connecting the 4.7 nH inductor, for example, as shown in Figure 5, the change of L3 affects the lower band resonance frequency and the second and third high resonant frequencies.

Figure 5: Reflection coefficient of the proposed antenna for different value of L3.

The simulated surface current distributions of the antenna on state 1 (connecting the 4.7 nH inductor) at 900 MHz, 1780 MHz, 2040 MHz, and 2640 MHz are shown in Figure 6, respectively. In Figure 6(a), it can be found that the current flows along the long grounded strip and the path length is nearly half wavelength at 900 MHz. As shown in Figure 6(b), when the antenna resonant frequency is at 1780 MHz, the surface currents mainly concentrate in the feeding L-shaped strip. In Figure 6(c), coupled currents flow on both the shorter and longer grounded strips, while in Figure 6(d) stronger currents flow in longer grounded strips.

(a)

(b)

(c)

(d)

Figure 6: Simulated surface current distributions of antenna 1 at (a) 900 MHz, (b) 1780 MHz, (c) 2040 MHz, and (d) 2640 MHz.

3. Results and Discussion

The photos of the fabricated antenna are shown in Figure 7. The ground and the strips on the top layer of the board are copper with tin coating. The foam is used to support the suspended copper strips during the measurement. On the bottom of the board, the “high” bias voltages on the two ports V1 and V2 are controlled by two AA batteries (placed in the black box), and the “low” bias voltages on the two ports V1 and V2 are controlled by the controlling lines connected to the GND. The voltage on port VDD is also connected to the GND. By changing the voltage level on ports V1 and V2 (in this paper, we change the inserting states of the wire pin in the circuit board), different states of the RF switch can be achieved.

Figure 7: Photos of the fabricated antenna.

The measured and simulated reflection coefficients are plotted in Figure 8. According to the results, for state 1, when 4.7 nH inductor is connected with the long grounded strip, the −6 dB measured impedance bandwidth can cover 792–960 MHz and 1485–2820 MHz. For state 2, when 13 nH inductor is connected, the measured −6 dB impedance bandwidth is 749–793 MHz and 1460–2720 MHz. For state 3, when 15 nH inductor is connected, the measured −6 dB impedance bandwidth is 717–760 MHz and 1485–2680 MHz. For state 4, when 18 nH inductor is connected, the measured −6 dB impedance bandwidth can cover 683–720 MHz and 1460–2620 MHz. The changes of states affect the lower frequency bands. This is because the inductors are connected with the longer grounded strip which controls the resonant modes of the lower band. Highest resonant frequency in the upper band is also affected; this is because the coupling between the two grounded strips is changed with different inductors. The differences between the measured and simulated results are mainly caused by the fabricating error and the change of the characteristics of the board and lumped elements according to the change of frequencies.

(a)

(b)

Figure 8: Measured (a) and simulated (b) reflection coefficients for the proposed antenna against frequency.

Figure 9 shows the measured and simulated normalized radiation pattern when the antenna operates at 900 MHz, 1900 MHz, and 2450 MHz, respectively. At 900 MHz, dipole-like radiation patterns can be observed, and for frequencies in the upper bands like 2450 MHz more nulls can be observed because of the higher-order mode of the antenna.

(a)

(b)

(c)

Figure 9: Measured and simulated radiation patterns for the proposed antenna: at (a) 900 MHz, (b) 1900 MHz, and (c) 2450 MHz.

The gain and radiation efficiency of the antenna are shown in Figure 10. In the lower band (683–960 MHz), the measured gain varies from −1.43 dBi to 2.28 dBi, while in the upper band (1460–2820 MHz) the measured gain varies from 0.42 dBi to 2.0 dBi. The radiation efficiency of the proposed antenna is greater than 50% in the lower band and greater than 60% in the upper band, which is acceptable for mobile handset application [9].

Figure 10: Antenna gain and radiation efficiency.

4. Conclusion

A compact antenna for mobile handset application was proposed. By simply changing the working states of RF switch, frequency reconfigurable performances can be fulfilled. With a size of 12 × 28 mm², the antenna can cover LTE700/GSM850/900 and GPS/DCS1800/PCS1900/UMTS2100/LTE2300/2500 bands. The measured gain, radiation efficiency, and other characteristics show the proposed antenna is competitive for multiband mobile handset applications.

Competing Interests

The authors declare that there is no conflict of interests regarding the publication of this paper.

Acknowledgments

This work was supported in part by the Natural Science Foundation of China (no. 41401572), Priority Academic Program Development of Jiangsu Higher Education Institutions (PAPD) and Jiangsu Innovation & Entrepreneurship Group Talents Plan, and the Postgraduate Innovation Project of Jiangsu Province.

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