ISRN Signal ProcessingVolume 2013 (2013), Article ID 148646, 8 pageshttp://dx.doi.org/10.1155/2013/148646

Research Article

Studies on Z-Window Based FIR Filters

Rahul Pachauri,¹ Rajiv Saxena,¹ and Sanjeev N. Sharma²

¹Department of Electronics & Communication Engineering, Jaypee University of Engineering & Technology, Guna 473226, India²Department of Electronics & Communication Engineering, Samrat Ashok Technological Institute, Vidisha 464001, India

Received 7 June 2013; Accepted 29 July 2013

Academic Editors: I. Guler and C. S. Lin

Copyright © 2013 Rahul Pachauri et al. This is an open access article distributed under the Creative Commons Attribution License, which permits unrestricted use, distribution, and reproduction in any medium, provided the original work is properly cited.

Abstract.

As per classification of the window functions, the Z-windows are grouped in the category of steerable side-lobe dip (SSLD) windows. In this work, the application of these windows for the design of FIR filters with improved filter parameters has been explored. The numbers of dips with their respective positions in the side-lobe region have been compositely used to tailor the window shape. Filter design relationships have been established and included in this paper. Simultaneously, an application of these Z-window based FIR filters in designing two-channel quadrature mirror filter (QMF) bank has been presented. Better values of reconstruction and aliasing errors have been achieved in contrast to the Kaiser window based QMF bank.

1. Introduction

The finite impulse response (FIR) filters are one of the prominent building blocks used in various applications of digital signal processing. These filters have got more popularity than infinite impulse response (IIR) filters because of their inherent stability and linear phase characteristics [1]. The straightforward approach to design the FIR filters is truncating the ideal impulse response using windows. Careful selection of window function reduces the ripples introduced by truncation in the frequency response of these filters [2]. In the literature, several categories of windows have been proposed [3, 4]. One of the important categories of windows is steerable side lobe dips (SSLD) windows in which deep dips can be steered in the side lobes. Tseng windows and Zhong windows (ZWs) are the examples of SSLD windows [5, 6]. The ZW proposed by Zhong et al. [6] has simple expressions in either of the domains, good overall spectral characteristics, SSLD property and easy and flexible design technique as compared to Tseng window. These features of ZW motivated us to study this window from the FIR filter design perspective.

Prior to this work, the design of FIR filters using ZW has also been reported by Sharma et al. [7] in which filter order and transition bandwidth (TBW) have been minimized at the cost of higher passband ripple (PBR) and stopband attenuation (SBA). The filters designed by Sharma et al. [7] are having SBA in the range of 18–42 dB with single dip steered at an appropriate location in the side lobes of ZW. Followed by this work, the ZW filter (ZWF) has been designed using the traditional window based approach by Pachauri et al. [8] in which the PBR and SBA has been minimized at the cost of higher filter order. The expression of the filter order was modified in [8] and was made directly proportional to the number of SSLDs introduced in the ZW. It has also been demonstrated in [8] that the half main lobe width (HMLW) of ZW varies with dip displacement up to a certain position and after that it becomes constant. If the dips are introduced below this threshold position then the filter order reduces and PBR and SBA increase [7], whereas the filter order increases and PBR and SBA decrease when the dips are inserted on the other side of the threshold position [8]. With this background on spectral response of ZW, the studies available in [7, 8], low pass filters have been designed using Z-window in this work. Performance of these filters has been studied by varying number of dips in ZW along with respective variation in their position. This study helped us in establishing an application of this filter in multirate signal processing.

The remaining part of this paper has been organized as follows. In the next section ZW has been introduced and its properties from the filter design perspective have been discussed. In Section 3, an algorithm to establish the empirical design relationships for ZWF has been developed. Simulation results and the performance analysis of the proposed filters are included in Section 4. Design of quadrature mirror filter (QMF) bank using this filter as a prototype has been carried out in Section 5. A comparative study with Kaiser window (KW) based QMF bank has also been performed. Finally, the paper is concluded in Section 6.

2. Characterization of Z-Window for Filtering Application

The basic concept in ZW proposed by Zhong et al. [6] is that the spectral window can be considered as a special LPF which only passes the DC component. The technique used for the designing of ZW is based on the frequency sampling method used for FIR filter design.

The ZW of length with SSLDs has been defined as [6] where,

In this window, instead of traditional approach to minimize the maximum side-lobe level (MSLL) with steepest descent or linear programming [9, 10], dips have been introduced at frequencies , , masking the magnitude spectrum of the window at these frequencies.

A window of length may have dips which must satisfy the following conditions: Condition (3) tells us that apart from finite set of frequencies: , where zeros of already exist, can be assigned anywhere in the side lobes region, that is, . The meaningfulness of the solution is guaranteed by (4) and (5) as they give the upper bound of the solutions.

It has already been shown in [6] that by steering number of dips and their respective positions in the side lobes of ZW, the characteristics of the window, that is, HMLW, MSLL, and side lobe fall of rate (SLFOR), can be varied. To illustrate the above parameters, a ZW with one steerable dip is shown in Figure 1. The normalized frequency in bins, which has been used to label the -axis of the magnitude spectrum of ZW, has been defined as [11] where is the window length and is the sampling frequency.

Figure 1: Plot for illustrating the definition of the various parameters of Z-window with , , and dip at 5.6.

Other important properties of ZW given in [6, 8] and observed in this work are as follows.(i)The dips can be steered in the side lobes anywhere between bins 1 and [6].(ii)The HMLW, MSLL, and SLFOR can be varied by varying the number of dips and their position in the side lobes. This follows from the simulation plots shown in Figures 2 and 3.(iii)The HMLW increases linearly with the increase in position of dips initially and after that it becomes constant [8].(iv)The MSLL decreases with position of dips, initially linearly, and after that it becomes almost constant. This behavior of MSLL is shown in Figure 4.(v)It follows from Figures 1 and 2 that if the dips are inserted in the vicinity of the HMLW and SLFOR are higher, while MSLL is higher than the minimum value which follows from Figure 4. This property has been used in this work to obtain ZWF with maximum value of far end stopband attenuation (FESBA).

Figure 2: Variation of MSLL and SLFOR of ZW by insertion of one dip for a window of length .

Figure 3: Variation of MSLL and SLFOR of ZW by insertion of two dips in a window of length .

Figure 4: Variation of MSLL with position of dips for a window of length .

The above listed properties of Z-window function are directly associated with the design of FIR filters. Thus, these properties of ZW have been exploited in this work to design FIR filters. In the proposed work, new empirical design relationships have been derived which provide more flexibility to vary the design parameters of ZWF, keeping desired specifications intact.

3. Filter Design Relationships

To design an FIR filter using window functions the following relationships are required [11].(a)Relationship between SBA () and window shape parameter—this expression provides the value of window shape parameter for the desired SBA. In ZW, SSLD property, that is, number of dips and their position , has been used to tailor the window shape. (b)Expression defining the relationship between SBA () and normalized window width parameter () [12–14]—this value of is then used to calculate the filter order to provide the desired filter transition bandwidth (TBW; ), at a specified sampling frequency (). The value of is given by To establish these relationships for the design of FIR low pass filters with ZW, the parameters, namely, , , and , were varied. The resulting variation in and is recorded in Table 1 and corresponding plots are shown in Figures 5 and 6. From these plots the empirical relations between , , , and have been obtained. The procedure for establishing these relationships has been described with the aid of a flow chart shown in Figure 7. Conventionally, in window based FIR filter designs, filter order is initialized to a very large value and for this fixed value of design relationships are enumerated [12–14]. However, in this study, instead of using fixed it has been taken as a variable. Therefore, in this work variations in the values of and SBA have been obtained by varying the number of dips and their positions as well as the filter order . The filter order and the number of dips have been used to change and when these parameters become insensitive to a further increase in the dip position as shown in Table 1. The empirical relations have been obtained by taking an initial value of , normalized passband frequency () = 0.2, normalized stopband frequency () = 0.3, and sampling frequency () = 1. To design the ZWF, dips can be inserted anywhere between and . Dips are steered in the vicinity of if small TBW is required, while position of dips is moved towards if a large FESBA is needed. These design relationships are suitable up to  dB and . However, if the desired SBA is more than 175 dB the number of dips may be increased by one for every 12–15 dB increment in SBA approximately. The limiting values of SBA range for different number of dips are shown in Table 2. Using Figures 5 and 6 following filter design relationships are obtained: These equations have been used to design FIR filters using ZW for a given set of specifications.

Table 1: Observations to establish design relationships for ZWF.

Number of dips,
Position of dips,
Filter order,
Normalized window width,
Stopband attenuation, (dB)

1
1
17
1.576
16.93

1.1
21
2.09
20.61

1.6
35
3.35
38.89

1.7
37
3.61
42.57

2
2
47
4.53
44.12

2.6
57
5.73
60.73

3
3
69
6.74
61.09

3.8
79
7.87
76.66

4
4
91
8.98
78.49

4
99
9.84
90.34

5
5
111
11.03
93.28

5
121
11.95
105.67

6
6
131
13.04
107.82

6
141
13.92
118.93

7
7
151
15.05
121.36

7
161
15.91
132.82

8
8
171
17.04
135.27

8
181
17.91
146.78

9
9
191
19.05
149.31

9
199
19.89
160.68

10
10
213
21.12
163.82

10
219
21.85
174.42

Table 2: Required number of dips and range of stopband attenuation.

Number of dips,
Range of SBA, (dB)

1
≤44

2
≤61

3
≤77

4
≤92

5
≤106

6
≤120

7
≤134

8
≤148

9
≤162

10
≤175

Figure 5: Plot of versus for ZW with different number of dips.

Figure 6: Plot of versus for ZW with different number of dips.

Figure 7: Proposed flow chart to obtain the design relationships.

4. Simulation Results and Discussion

The FIR filters using KW and ZW are simulated for establishing a comparative study as well as for determining the performance of the ZWF. Simulation results are shown in Figures 8, 9, and 10. ZWFs have been designed with one, two, and three dips. Three sets of different and (i.e., 1.5 and 23 dB/0.1 and 50 dB/0.01 and 74 dB) have been used. The order of filter , TBW, and FESBA has been recorded in Table 3 corresponding to these sets of and . ZWF response has been observed at the lower and upper bounds of dip positions, that is, at and . To establish a comparative study for every set of and , two KWFs have been designed: (i) with an order to satisfy the design specifications and (ii) with an order equal to the ZWF order. From the recorded observations the following conclusions regarding the filters performance have been drawn.(a)To satisfy desired set of filter specifications a comparatively lower filter order is required by KWF.(b)With dips steered at , ZWF has a sharp TBW than KWF for the same filter order.(c)FESBA for a ZWF can be increased by increasing the number of dips and/or by translating the position of dips from towards .(d)For the same filter order ZWF provides greater FESBA than KWF by placing the dips at .

Table 3: Comparative performance of LPF.

S. no.
Type of filter
Number of dips,
Position of dips
Filter order,
Desired (dB)
Desired (dB)
Transition band
FESBA(dB)

1
ZWF
1

23
1.5
23
0.0497
−36.59

ZWF
1
N/2
23
1.5
23
0.0770
−74.28

KWF
—
—
11
1.5
23
0.0861
−29.01

KWF ()
—
—
23
1.5
23
0.0652
−57.20

2
ZWF
2

51
0.1
50
0.0624
−60.29

ZWF
2
N/2
51
0.1
50
0.0891
−133.1

KWF
—
—
31
0.1
50
0.0934
−78.97

KWF ()
—
—
51
0.1
50
0.0818
−104.4

3
ZWF
3

77
0.01
74
0.0712
−86.85

ZWF
3
N/2
77
0.01
74
0.0892
−185.9

KWF
—
—
47
0.01
74
0.0988
−105.4

KWF ()
—
—
77
0.01
74
0.0824
−145.2

ZWF: ZW based LPF; KWF: KW based LPF.

KWF (): KW based filter with order of ZWF.

(a)

(b)

Figure 8: Frequency responses of LPF with , ,  dB, and  dB with insertion of one dip, (a) comparative frequency responses, (b) expanded view of passband.

(a)

(b)

Figure 9: Frequency responses of LPF with , ,  dB, and  dB with insertion of two dips, (a) comparative frequency responses, (b) expanded view of passband.

(a)

(b)

Figure 10: Frequency responses of LPF with , ,  dB,  dB with insertion of three dips (a) comparative frequency responses (b) expanded view of passband.

This comparative study established the fact that a trade-off can be achieved between TBW and FESBA for ZWFs by varying the number of dips and dip positions. To exploit this feature of ZWFs they have been used as a prototype filters for QMF banks in the next section.

5. ZWF Based QMF Bank

QMF bank has got wide applications in the area of signal processing specially in sub-band coding of speech signal, digital audio applications, communication systems, and short time spectral analysis [15]. In QMF bank, the input signal is split into two equally spaced frequency subbands by two-band analysis filters followed by twofold decimation. At the receiving end, the corresponding synthesis bank has twofold interpolation in both subbands followed by synthesis filters, and finally an adder is used to add both bands. The reconstructed output signal suffers from three types of distortions, that is, aliasing, amplitude or reconstruction, and phase distortion [15]. The aliasing error can be reduced by using a prototype filter with high FESBA, while the reconstruction error can be minimized using filters having sharp transition bands. As in ZW based filters, a trade-off can be achieved between these two parameters, a QMF bank has been designed with ZWF as a prototype filter, and their performance has been compared with KWF based QMF bank. To demonstrate its usefulness in this multirate signal processing application first lowpass prototype filters have been designed using ZW and KW with the following specifications: , ,  dB, and  dB.

Then by using the optimization algorithm proposed by Soni et al. [16, 17] QMF banks have been designed. Corresponding frequency responses and error plots are shown in Figure 11. A comparative study has been carried out in Table 4. From this study it is observed that when dips are translated from to aliasing error decreases. Optimum performance of ZWF based QMF banks has been obtained with dips steered at , providing lowest values of reconstruction and aliasing errors. This performance is better than the KWF based QMF bank designed with the same filter order.

Table 4: Comparative performance of QMF bank.

Type of QMF
Filter order,
Reconstruction error (dB)
Aliasing error (dB)
FESBA (dB)

ZWF, dips at
70
0.00649
2.319 × 10⁻³
−78.01

ZWF, dips at
70
0.0172
4.302 × 10⁻⁶
−123.2

ZWF, dips at
70
0.0127
2.584 × 10⁻⁷
−162.5

ZWF, dips at
70
0.00934
1.614 × 10⁻⁷
−175.6

KWF
40
0.02349
1.989 × 10⁻⁴
−90.74

KWZ ()
70
0.01243
1.007 × 10⁻⁶
−125.8

(a)

(b)

Figure 11: QMF filter banks with , ,  dB,  dB (a) comparative frequency responses (b) reconstruction error and expanded view of the aliasing error in the inset.

6. Conclusion

A study on Z-windows has been carried out in this work by steering number of dips at different positions to characterize the variations in their HMLW, MSLL, and SLFOR. These window parameters have been chosen, as they proportionately decide the TBW, SBA, and FESBA parameters of filters. Since the number of dips and their positions together tailored the window shape, they have been compositely employed as a window shape parameter for ZW. The relationships (i) window shape parameter versus SBA and (ii) SBA versus have been established to design a ZW based filter with desired specifications. Performance of ZWFs with different dip positions has been studied and compared with KWFs. For the same filter order ZWF provides a sharp TBW than KWF when dips are inserted at , but with small FESBA. Translation of dips from towards results in a ZWF with better FESBA than KWF, but at the cost of relatively higher TBW. To exploit this trade-off between TBW and FESBA, ZWF has been used as a prototype filter to design a two-channel QMF bank using the optimization algorithm proposed by Soni et al. [16, 17]. Comparatively small distortion values in the ZWF based QMF bank have been obtained. Applicability of this filter can be further explored in other multirate signal processing applications.

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