Wireless Communications and Mobile Computing
Volume 2018 (2018), Article ID 8514314, 9 pages
https://doi.org/10.1155/2018/8514314

Research Article

NOMA for Multinumerology OFDM Systems

Ayman T. Abusabah¹ and Huseyin Arslan1,2

¹School of Engineering and Natural Sciences, Istanbul Medipol University, 34810 Istanbul, Turkey
²Department of Electrical Engineering, University of South Florida, Tampa, FL 33620, USA

Correspondence should be addressed to Ayman T. Abusabah; asabah@st.medipol.edu.tr

Received 23 November 2017; Revised 21 February 2018; Accepted 28 March 2018; Published 9 May 2018

Academic Editor: Oğuz Kucur

Copyright © 2018 Ayman T. Abusabah and Huseyin Arslan. This is an open access article distributed under the Creative Commons Attribution License, which permits unrestricted use, distribution, and reproduction in any medium, provided the original work is properly cited.

Abstract.

Nonorthogonal multiple access (NOMA) is a promising technique which outperforms the traditional multiple access schemes in many aspects. It uses superposition coding (SC) to share the available resources among the users and adopts successive interference cancelation (SIC) for multiuser detection (MUD). Detection is performed in power domain where fairness can be supported through appropriate power allocation. Since power domain NOMA utilizes SC at the transmitter and SIC at the receiver, users cannot achieve equal rates and experience higher interference. In this paper, a novel NOMA scheme is proposed for multinumerology orthogonal frequency division multiplexing system, that is, different subcarrier spacings. The scheme uses the nature of mixed numerology systems to reduce the constraints associated with the MUD operation. This scheme not only enhances the fairness among the users but improves the bit error rate performance as well. Although the proposed scheme is less spectrally efficient than conventional NOMA schemes, it is still more spectrally efficient than orthogonal multiple access schemes.

1. Introduction

Cumulative and incessant demands on new services and applications, in addition to the great expansion in the number of connected devices, have led to a huge data traffic explosion and appearance of different application classes and classifications [1]. Thus, a strong need to boost the expected high data traffic has been recently emerged. Also, since it became obvious that next generation has to support high data rates, applications industry and academia agreed on the necessity of new and flexible radio access technologies (RATs) [2].

Multiple access (MA) techniques play a major role in the overall communication process. Since the first generation up until the fourth generation, MA techniques were distributing the users over the available resources orthogonally. For instance, time division multiple access, frequency division multiple access, code division multiple access, and orthogonal frequency division multiple access (OFDMA) are considered as orthogonal multiple access (OMA) techniques. Eventually, researchers have moved away from utilizing the resources in an orthogonal way to a nonorthogonal one, which they call nonorthogonal multiple access (NOMA) [3].

Power domain NOMA adopts multiplexing multiple users through sharing the same resources at the transmitter (TX). Furthermore, it uses successive interference cancelation (SIC) as a multiuser detection technique to separate the users through power differences at the receiver (RX) side. NOMA is considered as a promising multiple access technique for the fifth-generation wireless networks due to massive connectivity, low latency, and high spectral efficiency (SE) [4].

It is shown that, by adopting NOMA with orthogonal frequency division multiplexing- (OFDM-) based method as RAT, multiple users can be allocated on a subcarrier at the same time. However, the cochannel interference (CCI) per subcarrier increases as more users are multiplexed on the same subcarrier, which degrades the system performance [5]. In [6], the authors have studied users’ pairing; then they concluded that NOMA outperforms OMA especially with users whose channel conditions are more distinctive, which is practically difficult to occur.

Power control/allocation has been studied in many works [7]. To guarantee the fairness among NOMA users, more power is required for users with poor channel conditions and less power for users with better channel conditions [8]. However, if the users have similar channel conditions, OMA can guarantee better fairness and conventional power domain NOMA cannot strictly guarantee the users’ quality of service (QoS) targets [9], which could be critical for some scenarios with strict fairness constraints.

In this work, we propose an OFDM based NOMA scheme. The scheme utilizes the numerology concept to reduce the constraints associated with the conventional NOMA schemes. Simply, the users utilize different subcarrier spacings, wide subcarriers, and narrow subcarriers. A three-user scenario is considered in this paper. In the conventional scheme, the three users are supposed to share the same subcarriers as shown in Figure 1(a), while in the proposed scheme one user is assigned narrower and less frequently spaced subcarriers as illustrated in Figure 1(b).

(a) Carrier representation for conventional NOMA at the RX end

(b) Carrier representation for proposed NOMA at the RX end

(c) Time representation for conventional NOMA at the TX end

(d) Time representation for proposed NOMA at the TX end

Figure 1: Signals superposition in time and frequency domains.

The subcarriers configuration of the proposed scheme is characterized by the fact that the wide subcarrier users are fully overlapped within the same wide subcarriers and make a zero crossing at the peaks of the other wide subcarriers. Furthermore, the narrow subcarriers do not impose any interference at the peaks of wide subcarriers, that is, by avoiding the transmission on the half of narrow subcarriers. As a result, the wide subcarriers are not affected by any external interference. On the other hand, an interference is imposed by the tails of the wide subcarriers on the peaks of the narrow subcarriers.

Even though the narrow subcarriers share the bandwidth with the wide subcarriers, the detection, of wide subcarrier users, is independent of narrow subcarrier users; therefore, SIC can be used to detect the wide subcarrier users based on their power differences. On the other hand, the narrow subcarriers are detected once the interference imposed by wide subcarriers is eliminated.

By assigning one of the users narrower subcarriers, we reduce the amount of CCI imposed on the wide subcarrier users. Furthermore, the interference imposed on the narrow subcarrier user can be easily canceled by eliminating the wide subcarrier signals, which enhances the bit error rate (BER) performance for each user.

The narrow subcarrier user has an extra degree of freedom (DOF) as its power level is independent of the detection process; that is, it is not restricted to the wide subcarrier users and does not affect their detection process. In other words, the SIC process does not depend on the power level of the narrow subcarriers which grants more flexibility for power assigning. Based on that, the proposed scheme has the advantage of providing a fairer rate allocation to the users compared with the conventional scheme especially when the channel conditions of the users are similar.

The subcarriers configuration of Figure 1(b) can be simply accomplished by composing the symbols of wide subcarrier users synchronously in the time domain, that is, each with a length of one OFDM symbol slot. Then, the extended symbol, that is, narrow subcarrier user, is added. However, a novel structure is adopted for the transmission. As shown in Figure 1(d), the OFDM symbol slots of wide subcarrier users are orthogonally constructed and then the extended symbol of narrow subcarrier user is added. In this case, the wide subcarrier users are composed at the RX end and the proposed subcarrier configuration is obtained. In both transmission structures, the resulting signal consists of two OFDM symbol slots and the utilized resources are the same.

To achieve this purpose, a fast Fourier transform (FFT) operation, with the length of two OFDM symbol slots, is performed at the RX end. By doing this, the wide subcarrier users are multiplexed at the RX end. Extending the length of FFT window at the RX end allows us to equalize the channel using one cyclic prefix (CP) [10], which is a good solution to increase the SE even with an absolute OFDMA system.

The rest of the paper is organized as follows: Section 2 presents the signal configuration of the proposed scheme. Problem description, features, and potentials for our technique are provided in Section 3. The system model for conventional multicarrier NOMA scheme is given in Section 4. The design analysis is provided in Section 5. Simulation results are shown in Section 6. Finally, Section 7 concludes our paper.

2. Signal Configuration

The frequency and time representations, for conventional NOMA scheme, are shown in Figures 1(a) and 1(c), respectively. Three different power signals are multiplexed utilizing the same resources, where each signal constitutes one OFDM symbol slot; then a CP is appended. Therefore, the SE is expected to be doubled 3 times compared with OFDMA system without considering the CP redundancy.

On the other hand, in proposed NOMA, one of the users (user-2) is assigned narrower and less frequent subcarriers as illustrated in Figure 1(b), which simply multiplies the symbol duration by two as depicted in Figure 1(d). Since the new structure uses only seconds out of a possible , the SE, defined as bps/Hz, is halved for the wide subcarrier users. Meanwhile, as the total energy budget is the same, the power used by wide subcarrier users is twice as before. As the SE increases logarithmically with power, this increase does not compensate for the .5 loss in the SE; thus, the overall SE improvement over OFDMA is greater than 1 but strictly less than 1.5.

As mentioned earlier, the subcarriers’ configuration in Figure 1(b) can be obtained if both symbols of user 1 and user 3 share the first half of user 2 symbol. However, in Figure 1(d), user 1 and user 3 are constructed orthogonally at the TX. In this case, the subcarriers’ configuration of the proposed scheme is accomplished at the RX end where the wide subcarrier users (user 1 and user 3) are multiplexed by adopting an extended FFT operation.

In Figure 1(d), user 3 symbol is multiplexed with the first half of user 2 symbol and user 1 does the same with the second half. This can be seen from Figure 1(b) as well, where user 2 has a contribution from user 1 and user 3 at the peaks. Note that, user 1 and user 3 are orthogonal with respect to each other at the TX side. However, processing them together at the RX side, that is, by using an extended FFT window, makes them overlapping and therefore nonorthogonal. As the basic NOMA concept based on multiplexing the users at the TX utilizing the same resources, the proposed scheme can be considered as a half NOMA.

The key advantage of using larger FFT window size at RX is the capability of equalizing the channel using one CP for the whole OFDM symbols and thus increasing the SE. This property can be even used for a pure OFDMA system. For example, in the absence of user 2 in Figure 1(d), the system becomes an OFDMA system. Then, if FFT operation, with the length of two OFDM symbols, is performed at the RX, the transmitted symbols are composed and one CP can be used for equalization rather than two. In our case, the composed signals are detected in power domain and user 2 is able to share the other users’ resources without introducing any extra interference.

Note that user 2 signal (narrow subcarriers) makes a zero crossing with the other signals (wide subcarriers) at the peaks. This can be clearly concluded from frequency domain representation. The same result is not obvious from time domain representation. In Section 5, it is proven mathematically that, by adopting an extended FFT window size at the RX end, the wide subcarrier users are multiplexed although they are assigned different OFDM symbol slots at the TX and the narrow subcarrier users do not affect their detection process.

3. Problem Description

To describe the features of our proposed scheme, two scenarios are considered. The first scenario appears in Figure 2(a) where three downlink users have distinctive channel conditions , while the second scenario appears in Figure 2(b), where two users have similar channel conditions; that is, two users are at the cell edge and one user is close to the base station (BS).

(a) First scenario

(b) Second scenario

Figure 2: Two different user distribution scenarios: (a) and (b) .

In the case of the users whose channel conditions are similar, like the second scenario, either we assign similar power allocation (PA) to achieve the fairness and, therefore, SIC cannot work properly due to its inherent nature which depends on power differences for separation, or we assign different PA which leads explicitly to unfairness distribution.

3.1. Conventional NOMA (CN)

If users have distinctive as represented in Figure 2(a), under perfect channel state information assumption at the BS, achieving the fairness can be ensured through a proper PA. Furthermore, degradation in the performance due to the number of assigned users is expected. For instance, user 3 signal has to be detected with the presence of user 2 and user 1 signals by considering them as a noise, which degrades the BER performance.

In the second scenario, user 2 and user 3 experience the same channel effect. Therefore, if the fairness is a system requirement, both users have to be assigned similar PA. However, the natural work of SIC depends on the power differences to facilitate the separation process. Thus, with similar PA, the internal interference cannot be avoided and the performance can be extremely degraded.

3.2. Proposed NOMA (PN)

According to the first scenario, by assigning user 2 narrow subcarriers, we reduce the interference imposed on user 1 and user 3 signals. Thus, SIC process becomes easier since it has to differentiate two signals rather than three based on their power differences. Actually, the narrow subcarrier user is selected so that the other users, that is, wide subcarrier users, obtain more distinctive channel conditions. Besides, the PA of user 2 is determined independently which grants more flexibility for the system design.

This becomes very beneficial for the second scenario where achieving the fairness is an issue. As mentioned before, user 2 and user 3 cannot be paired as they have similar channel conditions. Nevertheless, if user 2 is assigned narrow subcarriers, user 3 and user 1 can be paired and a proper PA is determined. Naturally, the PA of user 2 is not restricted by the other users.

4. Conventional NOMA System Model

Conventional multicarrier downlink NOMA system is formulated by considering downlink users around a BS as shown in Figure 2. Users are distributed randomly and served by one BS and the total bandwidth consists of number of orthogonal subcarriers in frequency domain. Transceivers are supposed to be equipped with one antenna, and users share OFDM subcarriers through superposition coding.

The BS assigns different power levels depending on users’ conditions in order to achieve the fairness in the system and provide the capability of detection at the RX side using SIC. So, high power is assigned to the poor users, that is, far users, and low power to ones whose channel conditions are good. In other words, NOMA exploits the heterogeneity of users’ distribution and then allows the separation in the power domain [11].

The BS is transmitting the signal to the th user on the th subcarrier with transmission power , and, then, the received signal by user on subcarrier is given by [12] as follows:

where represents the additive white Gaussian noise (AWGN) for the th user on subcarrier with a zero mean and variance, that is, , and denotes the channel gain between the BS and the received user at the th subcarrier including both effects of large and small scale fading. Path loss and shadowing are considered as small fading effects. On the other hand, block Rayleigh is adopted for large-scale fading.

Without loss of generality, the channels are sorted as . For a given subcarrier, a user who enjoys a better downlink channel quality can decode and remove the CCI from a user who has a worse downlink channel quality by employing SIC [5]; thus, user enjoys a better channel quality than user . At the th user, if SIC is carried out perfectly, then achieving the fairness follows Shannon’s equation [13], where the achievable rate of the th user for Hz system bandwidth at the RX side is given by

where is the instantaneous signal-to-interference-plus-noise ratio by user on the th subcarrier and is the subcarrier bandwidth. Note that if the strongest user, that is, user 1, decodes and cancels all other users’ signals successively, then the achievable data rate is given by .

5. Signal Representation and Design Analysis

This section considers the design analysis of our proposed scheme. The mathematical model of the proposed scheme is established. The time domain signal in Figure 1(d) is formulated. Then, it is shown that, by adopting FFT operation with a length of two OFDM symbols at the RX side, the wide subcarrier users are composed although they are orthogonally transmitted.

Generation of wide subcarrier signals can be done using an inverse fast Fourier transform (IFFT) process with a length of samples. On the other hand, narrow subcarrier signals can be also generated using IFFT process with a length of samples, where is the ratio between the two different subcarrier spacings or the two different symbol lengths.

According to Figure 1(b), user 1 and user 3 signals are generated using IFFT with points, while user 2 signal is generated utilizing IFFT with points. It is worth mentioning that, to avoid direct interference with wide subcarriers, we do not use all of the narrow subcarriers for transmission. In our example, narrow-odd subcarriers are used for user 2 data transmission while narrow-even ones are filled with zeros using subcarrier mapping (SM).

An OFDM transmission symbol, of wide subcarrier user, is given by the point complex modulation sequence

where is the complex modulated symbol of th user on th subcarrier; that is, is the number of wide subcarrier users, is the assigned PA factor to the th user, and is the amount of power that is specified for wide subcarrier users.

In a similar way, the OFDM transmission symbol, for narrow subcarrier user, is given by the point complex modulation sequence

where is the complex modulated symbol of th user on th subcarrier after SM; that is, is the number of narrow subcarrier users, is the assigned PA factor to the th user, is the amount of power that is specified for narrow subcarrier users, is the total number of users, and the maximum assigned power from the BS to all users is ; that is, represents the conventional NOMA scheme case.

The wide subcarrier signals () are assigned different time slots to form one block with a length of samples. Thereafter, the narrow subcarrier signals () are added together forming another block which is already with a length of samples. Finally, the resultant blocks are added synchronously to produce one block with a length of samples for the transmission; this process can be expressed as follows:

According to the proposed scheme in Figure 1, , , , and . So (6) can be written as follows:

By assuming , (4) can be expressed as follows:

Since , the first half and second half of signal can be represented by setting to 0 and 1, respectively:

Thus, the second half of the signal is just a reversal copy of the first half because of odd subcarriers usage. From (9), the transmitted signal in (6) can be expressed as follows:

where represents the composed signal sample index .

After composing the signals, to avoid intersymbol interference and enable frequency domain equalization (FDE) at the RX, a copy from the resultant tail is appended as a CP where its duration has to be larger than the maximum excess delay of the channel.

At the RX end and after removing the CP, FFT operation, with a length of points, is performed as follows:

where are the received complex symbols after FFT operation. Afterwards, FDE takes the responsibility to get rid of channel’s sparsity where single tap equalization is available. To compute the output on the even and odd subcarriers, we assume that , and, then, (11) can be represented as

By setting and assuming for the second part of (12), then, the output on even subcarriers is proven to be

Explicitly, (13) proves that although and signals are constructed orthogonally at the TX, they are multiplexed by utilizing larger FFT window at the RX side. In addition, (13) ensures the absence of narrow subcarriers contribution to wide subcarriers; thereafter, SIC separates the wide subcarrier signals based on power differences.

User 1 and user 3 signals are constructed again; then, the reconstructed signal is subtracted from the received signal with a view to detect user 2 signal. Transceiver block diagram is given in Figure 3 for the proposed NOMA scheme.

(a) TX side

(b) RX side

Figure 3: Transceiver design for proposed NOMA scheme adopting three downlink users.

6. Performance Evaluation

In this section, we evaluate the performance of proposed NOMA scheme through simulation. System parameters are presented in Table 1.

Table 1: Simulation parameters.

Parameter name
Value

Number of wide subcarriers ()
64

Number of narrow subcarriers ()
128

Modulation type
QPSK

Total system bandwidth
5 MHz

Total power
10 dBm

The first scenario
20 dB, 17 dB, 0 dB for

The second scenario
20 dB, 0 dB, 0 dB, for

6.1. BER

The BER performance is supposed to be enhanced by performing proposed NOMA due to many reasons. Mainly, wide subcarrier users experience lower number of interferer users. Moreover, the interference imposed on narrow subcarrier user can be eliminated by detecting and canceling wide subcarrier users and utilizing the unused narrow subcarriers. Furthermore, the narrow subcarrier user can enjoy any power level. Thus, the BER performance is enhanced significantly. Note that the SINR values are considered at the RX side after FFT process.

The values utilizing conventional NOMA scheme for user 1, user 2, and user 3 on subcarrier , with successful decoding and no error propagation assumption, are given by

while values utilizing proposed NOMA scheme are expressed as follows:

Using the same PA for both schemes, we can notice from (14) and (15) that the first user experiences the same SINR values, while a big enhancement, in SINR values, is noticeable for the second and third user utilizing proposed NOMA.

6.2. Fairness Factor

To evaluate the fairness level for conventional and proposed NOMA we define the factor as in [14], where measures the equality of users’ rate for a given system and it is given by

For instance, if all users get the same amount of , then the value will be close to 1.

The goal of PA mechanism is to maximize the sum capacity under a fairness constraint for NOMA systems. The optimization problem is formulated as

where is the target fairness index in the network. The PA coefficients () are obtained through exhaustive search using algorithm 1 in [15].

According to the first scenario, the optimal PA coefficients utilizing conventional NOMA and proposed NOMA schemes are equal to and , respectively. On the other hand, based on the second scenario, the optimal PA coefficients utilizing conventional NOMA and proposed NOMA are found to be and , respectively.

Based on the obtained optimal PA coefficients, the BER performance is evaluated. The normalized channel gains () are set as in Table 1 and the fairness index is assumed to be 0.7. The individual BER for the first and the second scenarios are shown in Figures 4 and 5, respectively. Using the optimal PAs obtained for the second scenario, the fairness level, of conventional and proposed NOMA schemes, is evaluated as depicted in Figure 6. The results show clear dominance of proposed NOMA over conventional NOMA in terms of BER and fairness level.

Figure 4: BER performance utilizing the optimum PA for conventional and proposed NOMA in the first scenario, .

Figure 5: BER performance utilizing the optimum PA for conventional and proposed NOMA in the second scenario, .

Figure 6: Fairness level of conventional and proposed NOMA utilizing the optimum PA for the second scenario.

6.3. Spectral Efficiency (SE)

The spectral efficiency represents the amount of the carried data over the available resources. In [16], it is proven that the conventional NOMA schemes can offer a better SE than OMA. In conventional NOMA, the SE is expected to improve dramatically since three users utilize the available resources, that is, time and frequency units. Unfortunately, this comes at a price of unguaranteed QoS and loss of fairness. On the other hand, although proposed NOMA offers less SE than conventional NOMA due to additional time unit usage, that is, two time slots, it still provides superior SE compared with OMA. In particular, the superior SE in proposed NOMA arises from the capability of the narrow subcarrier user to share the available resources in addition to CP reduction between OFDM symbols.

The first scenario in Figure 2(a) is considered in the evaluation of the average SE for OMA, conventional NOMA, and proposed NOMA. For OMA, the bandwidth and the total power are split equally between the assigned users. The SE performance is illustrated in Figure 7.

Figure 7: Average spectral efficiency adopting conventional NOMA, proposed NOMA, and OMA using the optimum PA for the first scenario.

It is obvious from Figure 7 that the SE of proposed NOMA is decreased compared to conventional NOMA; however, it is still more spectrally efficient than OMA.

7. Conclusion

In this work, some of the NOMA-OFDM system based problems have been addressed by employing numerology concept cleverly. More DOF are given to one of the composed users by assigning narrower subcarriers. Based on this DOF, the constraints associated with the conventional NOMA schemes have been reduced and the BER performance has been improved too. Furthermore, the proposed method has proven its superiority in affording a fairer rate allocation to the users compared to conventional method.

A new methodology of multiplexing the users, in power domain, has been implemented by adopting a larger FFT window at the RX end. As a result, the guard durations between OFDM symbols became unnecessary. Thus, our proposed scheme is more spectrally efficient than OMA schemes.

Conflicts of Interest

The authors declare that there are no conflicts of interest regarding the publication of this paper.

Acknowledgments

The authors thank Khawar Hussain, Research Assistant, for assistance and comments that greatly improved the manuscript.

References

U. L. Rohde, A. K. Poddar, I. Eisele, and E. Rubiola, “Next generation 5G radio communication NW,” in Proceedings of the 2017 Joint Conference of the European Frequency and Time Forum and IEEE International Frequency Control Symposium ((EFTF/IFC), pp. 113–116, Besançon, France, July 2017.

J. G. Andrews, S. Buzzi, and W. Choi, “What will 5G be?” IEEE Journal on Selected Areas in Communications, vol. 32, no. 6, pp. 1065–1082, 2014.

L. Dai, B. Wang, Y. Yuan, S. Han, C. I, and Z. Wang, “Non-orthogonal multiple access for 5G: solutions, challenges, opportunities, and future research trends,” IEEE Communications Magazine, vol. 53, no. 9, pp. 74–81, 2015.

Z. Ding, Z. Zhao, M. Peng, and H. V. Poor, “On the Spectral Efficiency and Security Enhancements of NOMA Assisted Multicast-Unicast Streaming,” IEEE Transactions on Communications, vol. 65, no. 7, pp. 3151–3163, 2017.

Y. Sun, D. W. K. Ng, Z. Ding, and R. Schober, “Optimal joint power and subcarrier allocation for full-duplex multicarrier non-orthogonal multiple access systems,” IEEE Transactions on Communications, vol. 65, no. 3, pp. 1177–1191, 2017.

Z. Ding, P. Fan, and H. V. Poor, “Impact of User Pairing on 5G Nonorthogonal Multiple-Access Downlink Transmissions,” IEEE Transactions on Vehicular Technology, vol. 65, no. 8, pp. 6010–6023, 2016.

S. Timotheou and I. Krikidis, “Fairness for Non-Orthogonal Multiple Access in 5G Systems,” IEEE Signal Processing Letters, vol. 22, no. 10, pp. 1647–1651, 2015.

S. M. R. Islam, N. Avazov, O. A. Dobre, and K.-S. Kwak, “Power-Domain Non-Orthogonal Multiple Access (NOMA) in 5G Systems: Potentials and Challenges,” IEEE Communications Surveys & Tutorials, vol. 19, no. 2, pp. 721–742, 2017.

Z. DIng, X. Lei, G. K. Karagiannidis, R. Schober, J. Yuan, and V. K. Bhargava, “A Survey on Non-Orthogonal Multiple Access for 5G Networks: Research Challenges and Future Trends,” IEEE Journal on Selected Areas in Communications, vol. 35, no. 10, pp. 2181–2195, 2017.

J.-Y. Chouinard, X. Wang, and Y. Wu, “MSE-OFDM: A new OFDM transmission technique with improved system performance,” in Proceedings of the 2005 IEEE International Conference on Acoustics, Speech, and Signal Processing, ICASSP '05, pp. III865–III868, USA, March 2005.

A. Benjebbour, Y. Saito, Y. Kishiyama, A. Li, A. Harada, and T. Nakamura, “Concept and practical considerations of non-orthogonal multiple access (NOMA) for future radio access,” in Proceedings of the 2013 21st International Symposium on Intelligent Signal Processing and Communication Systems, ISPACS 2013, pp. 770–774, Japan, November 2013.

Z. Wei, D. W. K. Ng, J. Yuan, and H.-M. Wang, “Optimal Resource Allocation for Power-Efficient MC-NOMA with Imperfect Channel State Information,” IEEE Transactions on Communications, vol. 65, no. 9, pp. 3944–3961, 2017.

C. E. Shannon, “Communication in the Presence of Noise,” Proceedings of the IRE, vol. 37, no. 1, pp. 10–21, 1949.

R. K. Jain, D. M. W. Chiu, and W. R. Hawe, “A quantitative measure of fairness and discrimination for resource allocation in shared computer system,” vol. 38, pp. 20-21, Eastern Research Laboratory, Digital Equipment Corporation, Hudson, Mass, USA, 1984.

T. Manglayev, R. C. Kizilirmak, and Y. H. Kho, “Optimum power allocation for non-orthogonal multiple access (NOMA),” in Proceedings of the 10th IEEE International Conference on Application of Information and Communication Technologies, AICT 2016, Azerbaijan, October 2016.

P. Sedtheetorn and T. Chulajata, “Spectral efficiency evaluation for non-orthogonal multiple access in Rayleigh fading,” in Proceedings of the 18th International Conference on Advanced Communications Technology, ICACT 2016, pp. 747–750, kor, February 2016.