Long Range Backhaul Microwave Connectivity in Wireless Sensor Networks via a New Antenna Designed for ISM 2.4 GHz Band

This study aimed to explore a metallic striped grid array planar antenna, analyze it numerically in terms of its parameters, and optimize it for best performance. It may be an appropriate candidate for long-range point-to-point connectivity in wireless sensor networks. Antenna gain and frequency impedance bandwidth are two important performance parameters. For an eﬃcient antenna, its gain should be high while maintaining operating bandwidth wide enough to accommodate the entire frequency range for which it has been designed. Concurrently, antenna size should also be small. In this study, antenna dimensions were kept as small as possible without compromising its performance. Its dimensions were 300mm × 210mm × 9.9mm, which made it compact and miniature. It had a maximum gain of 16.72dB at 2.45GHz and maximum frequency impedance bandwidth of 7.68% relative to 50 Ω . It operated across a frequency band ranging from 2.38 GHz to 2.57GHz, encapsulating the entire ISM 2.4 GHz band. Its radiation eﬃciency remained above 93% in this band with a maximum of 98.5% at 2.45GHz. Moreover, it also had narrow HPBWs


Introduction
Wireless sensor networks usually have to communicate remotely to central monitoring systems. eir placement could be over large geographical area depending upon the intention of their deployment. Sensors that are deployed to monitor air pollution, wildfire detection, landslide detection, water quality monitoring, and natural disaster prevention reduce consumption of computational resources for future antenna designs, (iii) to propose a long-range antenna design for ISM 2.4 GHz band with characteristics of being lightweight, being easy to fabricate, low cost, being low in complexity, and high performance in terms of impedance bandwidth and gain with narrow beamwidth and high radiation efficiency.
Technologies such as Zigbee and Wi-Fi operating in ISM 2.4 GHz band can be employed as the standard for communication and in clustered wireless sensor networks, a head node responsible for relaying data of all nodes connected to it over long range [2]. Energy conservation is one of the prime objectives of wireless sensor network nodes while maintaining a reliable communication link to other nodes or central system. Directional antennas play a key role in long-range point-to-point communication in wireless sensor networks because they direct electromagnetic energy in narrow beams in particular directions, which not only increases range of communication but also maintains low energy constraints. Grid array antennas are known for their narrow frequency impedance bandwidth [3][4][5][6]. Any effort to improve the impedance bandwidth of these antennas can lead to deterioration of other performance parameters such as gain and radiation efficiency. erefore, optimized antenna design is required, which can operate with maximum performance in terms of all its parameters. Optimization of an antenna needs huge computing resources and time by employing traditional genetic algorithm techniques [7][8][9]. In this study, the proposed antenna is analyzed numerically first and then optimized for the best performance. Antenna optimization was carried out in parts to overcome the exhaustive computational problems. At first, a parametric analysis was carried out to narrow down ranges of antenna design parameters for which antenna performance was high. ese design parameters were the length of transmission line elements and the width of metallic strips. A suitable combination of length and width was chosen after analyzing data obtained from the parametric analysis where gain and frequency impedance bandwidth have high values relative to −9 dB value of reflection coefficient S 11 . e reason to choose −9 dB threshold of S 11 for calculation of frequency impedance bandwidth was to find out all those combinations of length and width, where a slight modification in design parameters could lead to maximum frequency impedance bandwidth relative to standard −10 dB value of S 11 . After inspection and selection of suitable length and width combination, a modification in the design of antenna was made and further parametric analysis was carried out. In the end, the quasi-Newton algorithm was applied for the finetuning purpose, which is computationally resource-efficient. e use of this strategy not only reduced computation time and resources but also results in a finely optimized antenna in terms of its performance.

Literature Review
e first grid array design was proposed by J. Kraus in 1964 [10], consisting of a grid of straight wires forming rectangular mesh parallel to a metallic ground plane. Each rectangle of mesh measures one wavelength by one-half wavelength. Broadsides of the mesh act as transmission lines, whereas short sides act as radiators. Current distributions in short sides were in phase with each other producing maximum radiation in a backward angle-fire direction. Frequency impedance bandwidth is affected by the distance between the grid and the ground plane. In 1981, R. Conti proposed the first nontraveling wave microstrip grid array antenna [11]. e antenna had control of aperture illumination, which minimized the side lobes. An analytical model was also developed for equivalent transmission line circuits of wire grids. e research team of Nakano et al. made several efforts to refine and optimize the grid array antenna further in terms of its performance. In 1994, they analyzed grid array antenna using the method of moment [3], where singularity and perturbation terms were extracted by impedance matrix. Furthermore, an interpolation technique was incorporated to minimize the computation time of the perturbation term. After the numerical analysis of current distribution, it revealed that antenna beam direction was the function of frequency. Also, it was observed that gain decreases when a substrate other than air was used. In 1995, they analyzed a center-fed antenna consisting of two orthogonal layers of grid arrays capable of radiating horizontally and vertically polarized beams [11]. e analysis revealed that the length of short edges should be 0.54λ and long edges should be 1.08λ; also the distance between grid and ground plane should be less than 0.2λ. In 1998, a meander line grid array antenna was analyzed by using the method of moment (MoM) for area reduction factor [4]; the gain dropped from 21 dB to 19 dB for a reduction factor of 38%. e reduction in size also leads to an increase in HPBW in the H plane, while it remained constant in the E plane. A C-figured grid array antenna was proposed to obtain a circularly polarized wave [5]. e antenna structure was analyzed by MoM. C figure elements were placed on both balanced and unbalanced fed grid array antennas separately to obtain circularly polarized waves; after that, reference grid array antennas were compared with C-figured grid array antennas and it was found that gain and HPBW had approximately the same values for both types of antennas. In a comparison of balanced C-figured grid array antenna to unbalanced C-figured antenna, it was found that although HPBW was the same in both cases, bandwidth of unbalanced C-figured grid array antenna was narrower than the balanced C-figured antenna. Further the cross mesh array antennas consisting of two antennas radiating dual linearly polarized and dual circularly polarized waves [12] were studied in 1999. In a similar work, a cross mesh antenna that was a combination of x-directed grid arrays and y-directed grid arrays having four feed points was proposed in 2001 [13]. e main aim of that research was to study the radiation characteristics of the new cross mesh array antenna. Right and left circular waves were generated separately when x-directed and y-directed arrays were excited. Right circular waves were generated when xdirected grid array was excited through its corresponding feed points. Similarly, left circular waves were generated when y-directed grid array was excited through its corresponding feed points. In another research, a news impedance matrix element for MoM was formulated to analyze the grid array antenna to reduce computation time as compared to the conventional impedance element [14]. In 2005, a new MoM technique was proposed to obtain current distribution along an arbitrarily shaped wire printed on a dielectric substrate having input impedance matrix elements consisting of single, double, and triple integrals conventionally [6]. e newly formulated input impedance matrices for two antennas, i.e., meander loop and grid array antennas, were analyzed and results were compared with the conventional impedance matrix element. Results showed that computation time was drastically reduced by a factor of 231 for meander loop antenna and 937 for the grid array antenna due to the new MoM technique. A two-layer rear space strip type grid array antenna using the finite difference time domain method was analyzed in 2006 [15]. Antenna rear space consists of two layers. On top, there was a layer of the substrate and, below that, there was a layer of air above the ground plane of the antenna. Antenna beam was narrow with small side lobes. It had a maximum directivity of 18 dB at 7 GHz with VSWR bandwidth of 13%. In 2007, a modified grid array antenna consisting of loop structure radiation elements was designed, which radiated circularly polarized waves [16]. It was a low-profile antenna with the frequency bandwidth of 2.3% and a maximum gain of 15 dB. e gain and direction of the beam of grid array antenna varied with frequency. As the frequency decreased the gain also decreased and vice versa. With an increase in radius of the loop frequency response curve shifted the radiation beams to lower frequency region. e antenna was consisting of 27 loops having a gain of 20 dBi.
As already discussed, a grid array antenna has narrow frequency impedance bandwidth and its input impedance is always greater than 50 Ω. Even the voltage standing wave ratio (VSWR) bandwidths in the cases of [3,6] were 1.5% and 2.6% relative to an input impedance of 55 Ω and 160 Ω,, respectively. So, it is important to increase frequency impedance bandwidth while keeping input impedance near 50 Ω of an antenna.
In 2008, Chen et al. optimized a microstrip grid array antenna using a parallel genetic algorithm [7]. At 2.45 GHz, antenna had a maximum gain of 18.3 dB, while its VSWR bandwidth was equal to 4.5% relative to 50 Ω. Radiating elements of the antenna were 13 similar to those of [15]. But an increase in the number of radiating elements also leads to an increase in antenna size. In 2010 [8], they proposed a novel antenna consisting of elliptical radiation elements and sinusoidal shaped transmission lines. e advantage of such an approach was that elliptical radiation elements improved frequency impedance bandwidth, while the use of sinusoidal transmission lines reduced the antenna size. e antenna was optimized using the genetic algorithm in combination with the finite difference in time-domain method. It took 110 hours on a cluster system to optimize. After optimization at 2.45 GHz, antenna had a maximum gain of 13.7 dB with 25% frequency impedance bandwidth. In 2013, they modified this antenna by using a linearly tapered ground plane and optimized it [9]. After optimization at 5.8 GHz, antenna had a maximum gain of 15.1 dB with frequency impedance bandwidth of 25.6%. Again, the optimization process takes 112 hours on a cluster system. In [8,9], optimization of antenna took too much time and resources. So, a technique was required which took low computational resources and time to optimize antenna design for best performance.

Design of Proposed Antenna
e antenna with dimensions of A × B (i.e., 300 mm × 210 mm) was designed, which had a structure of an ordinary grid array antenna as shown in Figure 1. e long side of a rectangular frame whose length was "L" acted as transmission line, while short side whose length was "S" acted as a radiator. e numbers of transmission lines and radiators were 8 each. e distance of the ground plane from the metallic grid was "H." e antenna was fed by coaxial cable via SMA connector. e substrate between the antenna and the ground plane was air. e width of the metallic strip was "W," while the thickness of the strip was fixed to 0.5 mm. Ansys HFSS (ANSYS Inc., Canonsburg, PA, USA) with an integral equation method was used to analyze the antenna parametrically for frequency impedance bandwidth and gain at frequency of 2.45 GHz.

Parametric Analysis
In the first stage of parametric analysis, antenna was analyzed to find out a combination of "L" and "W" at which it had high values of gain and frequency impedance bandwidth. Initially, values of "S" and "H" were kept fixed at S � 0.5λ and H � 0.08λ, respectively, while values of "L" and "W" were varied from 0.75λ to 1.25λ and from 0.01λ to 0.1λ, respectively, with an interval of 0.005λ. Frequencies at which analysis was carried out were ranged from 2.4 GHz to 2.5 GHz with an interval of 0.01 GHz (i.e., total 11 in numbers). After parametric analysis, further investigation was carried out on obtained data to find out all those combinations of "L" and "W," where gain and frequency impedance bandwidth had high values. ere were many combinations of "L" and "W," where antenna resonated two or more times on the entire frequency range. In between those resonances at some frequency range, it had values of the reflection coefficient S 11 slightly greater than that of −10 dB due to which it had narrow frequency impedance bandwidth. A slight modification in antenna design and optimization could fix that problem as it will be explained in the next sections of this article. So, after careful inspection of parametric data, all those combinations of "L" and "W" were separated, for which a minimum of 9 or more sampling frequencies out of 11 had S 11 values less than −10 dB. ose values of "L" and "W" are presented in Table 1 with corresponding S 11 , gain, and frequency impedance bandwidth values against frequency range from 2.4 GHz to 2.5 GHz with an interval of 0.01 GHz.
en, to identify all combinations of "L" and "W," where values of S 11 were slightly higher than -10 dB on the entire frequency range, the threshold level of S 11 was increased to International Journal of Antennas and Propagation −9 dB and new frequency impedance bandwidths were determined.
ese new frequency impedance bandwidths are presented in Table 1. All the above processes narrowed down values of antenna design parameters "L" and "W" for its maximum performance in terms of frequency impedance bandwidth and gain.
From Table 1, it can be observed that, at L � 140.7625 mm and W � 3.6750 mm, frequency impedance bandwidth has a maximum value of 4.08% relative to −9 dB threshold of S 11 , which covers entire ISM, 2.4 GHz band. Gain is also maximum at this combination of "L" and "W" having a value of −16.92 dB. If this combination was chosen for further optimization of the antenna, then there was a possibility of missing some combinations of "L" and "W" present in original parametric analysis data at which the value of S 11 is also less than −9 dB against each frequency from 2.4 GHz to 2.5 GHz. ose combinations of "L" and "W" could also be an equal candidate for further optimization of antenna provided gain was sufficiently high. So, frequency impedance bandwidth was plotted for −9 dB threshold of S 11 to verify the existence of any other combination of "L" and "W" at which impedance bandwidth has a maximum value. ese results were calculated while keeping the S 11 threshold value −9 dB relative to 50 Ω. Frequency impedance bandwidth is determined by the following formula: where f max and f min are maximum and minimum frequencies between which values of S 11 remained less than or equal to −9 dB. Figure 2(a) presents a relationship between frequency impedance bandwidth and length and width of radiation elements after first parametric analysis. Frequency impedance bandwidths were set to zero for all those combinations of "L" and "W," where antenna did not resonate on the entire frequency range because at those combinations frequency impedance bandwidth cannot be determined. From  Figures 2(b) and 2(c), it can be observed that maximum bandwidth is laying around L � 0.87λ and W � 0.03λ; that is, L � 140.7625 mm and W � 3.6750 mm, respectively. So, the antenna has maximum frequency impedance bandwidth on this combination of "L" and "W." Similarly, Figure 3(a) represents the variation of reflection coefficient S 11 for "L" and "W." Figures 3(b) and 3(c) represent the reflection coefficient parameter S 11 concerning 50 Ω reference impedance against "L" and "W," respectively. Values of S 11 for all those combinations of "L" and "W" for which antenna did not resonate for the entire frequency range were set to zero. e majority of minimum values of S 11 lie between L � 136 mm and 146 mm and between W � 2.4 mm and 8.6 mm.
Simulated gain with respect to "L" and "W" is shown in Figures 4(a) and separately in Figures 4(b) and 4(c) against variations of "L" and "W," respectively. It can be noted that maximum gain of 16.92 dB is also around L � 0.87λ and W � 0.03λ, that is, at L � 140.7625 mm and W � 3.6750 mm, respectively.
So, from the above discussion, it can be concluded that antenna has maximum gain and frequency impedance bandwidth around L � 0.87λ and W � 0.03λ (i.e., at L � 140.7625 mm and W � 3.6750 mm). But, to meet the standard, antenna frequency impedance bandwidth should be maximum against −10 dB threshold value of S 11 . At L � 140.7625 mm and W � 3.6750 mm, antenna resonated two times around 2.41 GHz and 2.48 GHz. Values of S 11 were less than −10 dB for the entire ISM band except for 2.44 GHz to 2.46 GHz, where they were slightly higher than −10 dB, that is, between −9.75 dB and −9.37 dB, as shown in Figure 5. So, bandwidth was narrow for both resonances. To expand frequency impedance bandwidth relative to −10 dB of S 11 , a modification in antenna design was made by introducing a resistor "R" to connect the metallic grid and ground plane electrically. e resistor reduces antenna input impedance, which increases in frequency impedance bandwidth [17]. International Journal of Antennas and Propagation e introduction of the resistor also increases ohmic losses of the antenna, which may lead to a decrease in antenna radiation efficiency and its gain. Proper placement of the resistor was necessary to estimate its effects on frequency impedance bandwidth and gain of the antenna at 2.45 GHz. Again, Ansys HFSS with the IE method was used to parametrically analyze the antenna in the second stage. is time parametric values of S � 0.5λ, H � 0.08λ, L � 0.87λ, and W � 0.03λ were fixed. e dimensions G and R were varied from 0.25λ to 0.67λ and from 1 Ω to 50 Ω with an interval of 0.01λ and 1 Ω, respectively.
Simulated frequency impedance bandwidths against G and resistance R are shown in Figure 6 Figures 7(a)-7(c) depict the reflection coefficient S 11 concerning reference impedance of 50 Ω against parameters G and R, respectively. Again, values of S 11 for all those combinations of G and R, where antenna did not resonate on the entire frequency range, were set to zero. It can also be noted that S 11 has the lowest values between G � 55 mm and 75 mm and between R � 35 Ω and 45 Ω with a minimum value at G � 74.7250 mm and R � 41 Ω.
e gain of the antenna at frequency of 2.45 GHz is shown in Figures 8(a)-8(c). Variation in resistor R value has almost no effect on it as demonstrated in Figure 8(b), but it gradually increased with an increase in the value of G, as shown in Figure 8(a). At G � 74.7250 mm and R � 41 Ω it has maximum value of 16.74 dB.
After the second stage of parametric analysis, the value of the reflection coefficient parameter S 11 remained less than −10 dB for the entire ISM 2.4 GHz band at G � 0.61λ (i.e., at 74.7250 mm) and R � 41 Ω as shown in Figure 9. However, it had a value of approximately −10 dB at 2.40 GHz, which limits frequency impedance bandwidth beyond 2.40 GHz. To further enhance the impedance bandwidth, a light optimization was carried out so that antenna can operate in the ISM 2.4 GHz band and beyond.

Antenna Optimization
For optimization of antenna, again Ansys HFSS was used, where the quasi-Newton algorithm with IE methodology was applied. e antenna was fed with a coaxial cable at wave port. e material between antenna and ground plane was considered as air. Metallic grid and ground plane were assumed to be made of copper sheets of finite conductivity of 5.8 × 107 S/m and 0.5 mm thickness.
Only International Journal of Antennas and Propagation 7 entire ISM band with frequency impedance bandwidth of 7.27% as shown in Figure 10. At 2.45 GHz, total gain was 16.72 dB in zx-plane and zyplane, while half power beamwidth (HPBW) in these planes was 18.52°and 31.25°, respectively, as illustrated in Figures 11(a) and 11(b). ese measurements of HPBW indicate that antenna has narrow beamwidth with high power and therefore it is less prone to interference.
Antenna radiation pattern indicates its narrow beam, as shown in Figure 12.

Results and Discussion
Antenna gain can be enhanced by increasing the number of radiation elements in it, but it causes an increase in its size as well. In our proposed antenna design, the number of radiation elements is 8, i.e., one more than [8,9]. But an increase in the number of radiation elements did not affect its size; instead, it remained compact. After optimization, the maximum gain of the antenna at 2.45 GHz was 16.72 dB with a frequency impedance bandwidth of 7.68%.  Meanwhile, antenna radiation efficiency remained above 93% with a maximum value of 98.54% at 2.45 GHz. HPBW of the antenna was 31.25°and 18.52°in horizontal and vertical planes, respectively. Table 2 presents a performance comparison of our proposed antenna with previous works. Figure 13 shows the current distribution along transmission lines and radiation elements of the antenna at 2.45 GHz. At this frequency, the antenna has maximum gain and radiation efficiency values because currents are concentrated mainly along with seven radiation elements represented by black vectors, where they are added in phase and result in radiation pattern, while in transmission lines currents are mutually exclusive and opposite in direction in terms of far field as shown by white vectors. So, seven radiation elements act as dipole and generate radiation patterns. Gain and radiation efficiency both tend to decline at frequencies less or greater than 2.45 GHz because of an increase in the misalignment of current vectors along with radiation elements at these frequencies.

Radiation Efficiency
Antenna radiation efficiency against frequency is depicted in Figure 14, which is 98.54% at 2.45 GHz, while it remained above 93% for the entire ISM 2.4 GHz band.

Gain
e gain of antenna remained high for the entire ISM 2.4 GHz range with a maximum of 16.72 dB at 2.45 GHz, as shown in Figure 15. It reduced as wavelength increased because the distance between the ground plane and the grid is dependent on wavelength and antenna gain is sensitive to this distance [19] but even then it remained above 14.7 dB at 2.5 GHz. Reduction in the gain of 2 dB is in acceptable range because it is less than 3 dB, which is standard for communication links. International Journal of Antennas and Propagation

Half Power Beam Width (HPBW)
HPBW of the antenna is depicted in Figure 16 where it can be seen that in zx-plane HPBW varied from 18°to 19°for the entire frequency range. Similarly, it varied from 30.75°to 31.75°in zy-plane.

Antenna Fabrication
Antenna grid array frame and the ground plane were fabricated by a sheet of copper of 0.5 mm thickness. e optical laser cutting technique was used to cut the grid array frame according to measurement. e frame was raised by ground plane by Teflon pieces having a height equal to that of substrate, that is, 9.9 mm. Figures 17(a)-17(c) give front, side, and back views of antenna, respectively. Measurements of antenna gain and reflection coefficient S 11 were carried out. From S 11 measurement, it can be observed that antenna operates between 2.39 GHz and 2.57 GHz having frequency impedance bandwidth of 7.65%. S 11 plot against frequency range from 2.3 GHz to 2.6 GHz is shown in Figure 18.

Link Budget Calculation
To estimate the potential range and performance of the proposed antenna over the long range, the link budget is calculated for it. According to [20], power received by a receiver at a distance "D" (Km) at frequency "F" (GHz) is estimated by the formula where P r is the received power in dBm and P t is the transmitted power in dBm. G t is the gain of transmitter antenna in dB. G r is the gain of receiver antenna in dB, L fs is free space loss in dB, and L is combined loss due to connectors and cables on both transmitter and receiver side, which is also measured in dB. In equation (2) P t , G r , and G t are straight values, while L fs and L are combinations of different parameters. L fs can be defined as L fs � 20 log 10 D + 20 log 10 F + 92.45.
Similarly, L of equation (2) is a combination of cable losses plus connector losses on both transmitter and receiver sides. So, L cable is loss due to cable measured in dB. For the computational purpose, we have taken LMR600 cable having an impedance of 50 Ω into consideration, which has 0.14 dB loss per meter. L cable is multiplied by a factor of 2 because on both transmitter and receiver sides approximately the same length of cables is being used due to antenna height with respect to ground. e height of the antenna is the sum of Fresnel zone around a point-to-point link and curvature of Earth between transmitter and receiver. Both these two heights are measured in meter. So, L cable can be defined as where H Fresnel is the antenna height due to Fresnel zone and H curvature is the antenna height due to curvature of the Earth, which is also measured in meters. For the safe side instead of taking 60% of the first Fresnel zone, all first Fresnel zones are considered here for link calculation. H Fresnel can be defined as Similarly, the curvature of Earth between two points can be defined as × 1000. (7)  Putting equations (6) and (7) in equation (5), L cable became L cable � 0.14 × 17.32 In equation (4), L connector is lost due to an SMA connector, which is multiplied by a factor of 4 assuming a total of four SMA connectors used on both the transmitter and receiver sides. Two connectors are used to connect the transmitter and transmitting antenna, while the other two are used to connect the receiver and receiving antenna. e insertion loss of the SMA connector depends on the frequency, which can be defined as Putting equations (8) and (9) in equation (4), loss due to cables and connectors became L � 2 × 0.14 × 17.32 × 1000 + 4 ×(0.03 If transmitter antenna transmits 20 dBm power and both transmitting and receiving antennas are the same, which have been fabricated in this research to have a gain of 16.72 dB, then, putting values of P t , G t , G r , L fs , and L in equation (2), Assuming −95 dBm sensitivity of receiver, a graph between distance "D" and received power P r at frequency F � 2.45 GHz is shown in Figure 19.
From Figure 20, it can be seen that even at a distance of 20 Km fade margin is still approximately 6 dBm and the signal has considerable strength with respect to the sensitivity of the receiver. So, the antenna can be a suitable candidate for long-range communication in ISM 2.4 GHz band due to its high gain characteristic.

Conclusion
In this research work, a metallic grid array antenna was designed, which operates in ISM 2.4 GHz band and provides long-range connectivity. e antenna performance in terms of frequency impedance bandwidth and gain was studied. To improve performance, modifications in antenna designs were made. Later, a light optimization was carried out to tune up its performance further. e antenna has high gain, high radiation efficiency, low complexity, and narrow beamwidth. ese characteristics make it an ideal candidate for long-range communication in ISM 2.4 GHz band.
Data Availability e data used to support the findings of this study are included within the article.

Disclosure
Syed Mushhad Mustuzhar Gilani and Muhammad Tamur Sultan are co-first authors.

Conflicts of Interest
e authors declare that there are no conflicts of interest regarding the publication of this paper.

Authors' Contributions
Syed Mushhad Mustuzhar Gilani and Muhammad Tamur Sultan contributed equally to this work. Syed Mushhad Mustuzhar Gilani supervised and provided intellectual support at each step of this research work. He suggested improvements in the main idea of the research, antenna optimization, and writing of the manuscript. He analyzed the proposed approach and evaluated the obtained results. Mr. Muhammad Tamur Sultan presented the main idea for antenna design, designed it, simulated it, acquired data, and then interpreted it in the form of results. He also performed parametric analysis. Mr. Zeng Shuai contributed with the expert's advice for manuscript drafting, helped in taking practical measurements of antenna fabrication for its performance parameters, and also arranged funding for this research study. Mr. Asif Kabir contributed in revising this research work critically for its important intellectual content so that it can be presented suitably for the publication. All authors read and approved the final manuscript.