Active Equalization Strategy for Lithium-Ion Battery Packs Based on Multilayer Dual Interleaved Inductor Circuits in Electric Vehicles

Lithium-ion batteries (LIBs) are widely used in electric vehicles (EVs) due to their superior power performance over other batteries. However, when connected in series, overcharged cells of LIBs face the risk of explosion, and undercharged cells decrease the life cycle of the battery. Eventually, the inconsistency phenomenon between cells resulting from manufacturing tolerance and usage process reduces the overall charging capacity of the battery and increases the risk of explosion after long-time use. Research has focused on synthesizing active material to achieve higher energy density and extended life cycle for LIBs while neglecting a comparative analysis of equalization technology on the performance of battery packs. In this paper, a nondissipative equalization structure is proposed to reconcile the inconsistency of series-connected LIB cells. In this structure, a circuit uses high-level equalization units to enable direct energy transfer between any two individual cells, and dual interleaved inductors in each equalization unit increase the equalization speed of a single cell in one equalization cycle by a factor of two. *e circuit is compared with the classical inductor equalization circuit (CIEC), dual interleaved equalization circuit (DIEC), and parallel architecture equalization circuit (PAEC) in the states of standing, charging, and discharging, respectively, to validate the advantages of the proposed scheme. Considering the diversity of imbalance states, the state of charge (SOC) and terminal voltage are both chosen as the equalization criterion. *e second-order RC model of the LIB and the adaptive unscented Kalman filter (AUKF) algorithm are employed for SOC estimation. For effective equalization, the adaptive fuzzy neural network (AFNN) is utilized to further reduce energy consumption and equalization time.*e experiment results show that the AFNN algorithm reduces the total equalization time by approximately 37.4% and improves equalization efficiency by about 4.89% in contrast with the conventional mean-difference algorithm. Particularly, the experiment results of the equalization circuit verification certify that the proposed equalization structure can greatly accelerate the equalization progress and reduce the equalization loss compared to the other three equalization circuits.


Introduction
EVs have attracted increasing attention in recent years due to their efficient energy utilization, zero emissions, and contributions to carbon neutral and green global environment. EVs commonly use LIBs characterized by superior power performance, long life, high-energy density, and no memory effect [1,2]. However, the electrical capacity, voltage, and instantaneous discharge power of individual LIB cell are far below electricity demand in real-world applications. us, LIB cells are often connected in series to boost the voltage and in parallel to increase the capacity [3]. Different from cells connected in parallel that are able to self-balance the charge, cells connected in series are faced with the problem of cell charge imbalance that worsen over time [3][4][5]. In Figure 1, multiple cells are connected in series to form a string with a high voltage level. e charge of cells differs owing to the capacity, self-discharge rate, internal impedance, and temperature mismatch. Manufacturing differences and discrepancies in the usage environment reduce the overall battery performance, which accelerates battery aging and causes safety hazards (e.g., a fire or, in the worst case, an explosion) [6][7][8]. ese issues are worsened by the fact that LIBs are very sensitive to deep discharge and overcharge [9]. Numerous studies have been conducted to improve the capacity and life cycle of LIBs, and the safety issues have not been well addressed [10]. Manufacturing differences are inevitable, and thus a proper equalization technology is needed to make each cell operate safely and reliably.
e essence of equalization technology is to lower as much as possible the charge variance by equalization circuits and equalization control algorithms. e equalization technology is classified into passive and active according to the energy consumption and energy transfer [11]. e passive equalization technology dissipates the excess power of a higher SOC cell by power resistors, and yet it has two distinct drawbacks: energy waste and thermal imbalance. e delayed thermal consumption results in high local temperature of the battery pack, which may be a safety hazard [12]. e active equalization technology solves these two drawbacks by moving the excess power from higher SOC cells to lower ones via capacitors, inductors, or transformers [12]. e charge imbalance is resolved by energy deallocation. Particularly, the inductor-based active equalization circuit has wide acceptance because of good controllability and reliability [13]. In this paper, based on the CIEC, an inductor-based multilayer dual interleaved equalization circuit (MLDIEC) is proposed. e MLDIEC avoids inefficient transmission of energy when two battery cells are far apart with the aid of a high-level equalization unit. Incorporating dual interleaved inductors into the circuit enhances the equalization efficiency. Meanwhile, theoretical calculations are carried out to explore the relationship among different equalization parameters.
An equalization control strategy complementary to the equalization circuit is presented to illustrate the equalization processes. Generally, equalization control strategies can be based on the terminal voltage, SOC, or capacity, depending on the battery characteristics. Note that these variables can also be used as criteria to determine whether the battery pack is balanced. e terminal voltage of the battery is measurable in real time with a simple monitoring system, but it cannot describe the charge in the SOC-open-circuit voltage (OCV) plateau accurately [14]. e SOC takes into account many factors (e.g., the voltage, current, and internal resistance environmental temperature), yet it cannot be measured directly. Instead, the SOC needs to be calculated with various methods, e.g., the electrochemical model, the equivalent circuit method, and neural networks. e complexity of these methods limits their applicability of the SOC-based strategy [13]. e capacity-based strategy considers the aging rate besides SOC. Yet, the battery capacity is only available offline, and thus this method is not suitable for real-time applications [11]. In practice, the terminal voltage and SOC are adopted in different regions of the SOC-OCV characteristic curve of LIBs [15]. In the low and high voltage regions of the curve, the terminal voltage-based strategy is adopted to prevent overcharging or discharging [16]. In the plateau region, the SOC-based strategy is preferred since it describes the battery charge accurately. To achieve high accuracy in real-time applications, the SOC value can be estimated by the Kalman filter algorithm based on an equivalent circuit model. e improved unscented Kalman filter (UKF) proposed by J. C Lv estimates SOC with the error of just 0.63% [17,18]. us, the AUKF is employed for SOC estimation. e equalization control strategy incorporates an equalization algorithm [19,20]. e mean-difference algorithm is widely applied to the inductor-based equalization circuit due to its simplicity. However, the mean-difference algorithm is inefficient since it cannot maximize the overall performance of the equalization circuit [21]. erefore, we employ the AFNN to develop the equalization algorithm.
is algorithm is suitable for real-time operations, is very adaptive, and realizes nonlinear mapping with arbitrary accuracy. us, the AFNN is suitable for complex controlled objects that are challenging to be described by a mathematical model of the battery pack [22]. Figure 2 shows the overall structure of the proposed MLDIEC and its control strategy. e SOCs and terminal voltages of cells marked in the diagram are chosen to judge the equalization status of the battery pack. e AUKF is used for SOC estimation. e AFNN is adopted to improve the equalization efficiency. e rest of this paper is organized as follows. Section 2 introduces the structure and operating  principle of the MLDIEC. Section 3 describes the AUKF to estimate the SOC. Section 4 presents the equalization control algorithm in detail. Section 5 presents the experiment results. Section 6 concludes the paper. [23] proposes a CIEC, where an inductor is put between two adjacent cells to transfer energy from a high SOC cell to a low SOC cell, as illustrated in Figure 3. However, the energy transfer is limited to adjacent cells. Bo Dong et al. [4] proposed a multilayer inductor equalization circuit (MLIEC). With this circuit, energy is exchanged directly between two cells far apart, avoiding intermediate inductors and reducing energy loss during equalization [24,25]. Inductors in the CIEC and MLIEC are operated with asynchronous current to prevent inductor saturation but make inductor inefficient during equalization [26]. To overcome this drawback, we propose a multilayer dual interleaved equalization circuit (MLDIEC) based on the MLIEC, as shown in Figure 4(a). Figure 4(b) shows an equalization unit EU1-1 in greater detail, including two inductors (L1 and L2) and four MOSFETs (S1, S2, S3, and S4). High-layer units are utilized to transfer energy between any two cells, which speeds up the equalization, increases the battery energy usage, and reduces energy loss. e dual inductors replace the conventional single inductor and increase the cell operating time during an equalization cycle. is way, the circuit avoids keeping the battery idle for a long time and increases the equalization speed. e layer number and unit number per layer are determined by equations (1) and (2), respectively:

The MLDIEC
where m is the number of equalization layers, n is the number of cells in the series-connected battery, [− ] represents the Gaussian rounding function, and a is the number of equalization units in layer i.

Working Principle.
e equalization unit is a dual interleaved inductor unit that increases the cell operating time in an equalization cycle. Yet, a battery cell cannot be charged and discharged to two inductors simultaneously, which reduces the energy transfer efficiency. To address this issue, the phase difference between the pulse width modulation (PWM) signals of the two inductors can be set to 180°, so that the two inductors can compensate each other, and the battery operates safely. Take the EU1-1 in Figure 4(b) as an example. e two inductors work in Discontinuous Conduction Mode (DCM), and their operations are the same [27]. Assume that the SOC of B1 is higher than that of B2 to analyze the operating state of inductor L1. e equalization control switch S1 is controlled to achieve battery equalization at first. e equalization process within an equalization cycle T is divided into three stages based on the direction of energy transfer. e signal waveform of the three stages is shown in Figure 5, and the D is the duty cycle.
Stage 1: (0-t 1 (DT)). When the control signal from the equalization control system is set, switch S1 is turned on. Battery B1, inductor L1, and switch S1 make up a closed loop. e electric energy is converted into magnetic energy and stored in L1. According to the Kirchhoff laws (KCLs), the voltage relationship of the loop is obtained by

Journal of Advanced Transportation
e current of L1 is as follows: where R T-on is the total equivalent resistance of L1, S1, and B1 and the wire when S1 is turned on, L 1 is the inductance of L1, and V B1 is the battery voltage, which can be regarded as constant because the voltage does not vary much during a single period. When t reaches t 1 , B1 finishes discharging. e current of L1 reaches the maximum value in this equalization cycle. Stage 2: (t 1 -t 2 ). When switch S1 is turned off, a loop consists of B2, L1, and S2 is formed. At this stage, the magnetic energy stored in L1 is released. Similarly, the voltage of the loop is given by e current of L1 is found to be where R T-off is the equivalent internal resistance sum of L1, B2 and the wire when S1 is turned off, which can be approximately as R T-off � R T-on � R T , V B2 is the voltage value of B2 but is a constant, and V D is the on-state voltage drop of the parasitic diode of MOSFET S2 [28]. At time 0.5 T, switch S3 is turned on. Another loop is made up of B1, L2, S3. e electric energy of B1 is converted into magnetic energy, and stored in L2.

Stage 3: (t 2 -T).
At the end of stage 2, all the energy of inductor L1 transfers to B2. Stage 3 aims to prevent stage 1 of the next cycle from overlapping with stage 2 of the current period, which avoids energy accumulation in inductors.   V D in the two equations, the current of L1 is changed as follows:

Equalization Circuit
Assuming that t is equal to T, the duty cycle D and voltages should meet the following requirement: A relationship between D and voltages is thus developed as To make the inductor in DCM, V B2 should equal V B1 . erefore, the maximum theoretical value of duty cycle D is 0.5. Furthermore, based on the inductors operated in DCM and the current of L1 in one equalization cycle, the maximum energy transfer ratio of an individual inductor in the first-level equalization unit can be formulated as where Q v can also be interpreted as the average current value of the inductor, and f is the switching frequency.

Inductor and Square Wave Frequency.
To avoid battery damage from excessive current during equalization, the maximum current supplied to the battery should be below the peak current. e equalization circuit is designed as a hierarchical structure by considering that the current of different layers may superimpose on the battery. e inductor peak current of the equalization unit per layer is the same as that of the first layer. us, we obtain where V B-MAX is the upper limit voltage, i B-Define is the maximum equalization current allowed, m is the number of equalization layers, and f is the square wave frequency reflecting the relationship between the switching frequency of the MOSFET and the losses during equalization.

Switching Voltage.
e MOSFET employs switching frequency to control the current during equalization. e maximum withstanding voltage of the MOSFET must be greater than the voltage applied at both ends, preventing it from breaking down. As seen in Figure 5, the voltage across the MOSFET at the disconnection moment is the battery voltage. However, the MOSFET in each layer withstands the different voltage, increasing with the number of layers. e maximum withstand voltage of the MOSFET is where V max is the maximum voltage of an individual cell, and m is the number of equalization layers.

SOC Estimation Based on AUKF
e SOC estimation accuracy is directly affected by the performance of the equalization control algorithm. To make an accurate estimation, this paper employs a second-order equivalent circuit model considering the battery hysteresis effect and uses AUKF to estimate the SOC. e Kalman filter algorithm combined with the second-order equivalent circuit model estimates the SOC accurately in real-time applications. Meanwhile, the extended Kalman filter (EKF) and cubature Kalman filter (CKF) are employed as benchmarks.

Second-Order Equivalent Circuit Model.
Much effort has gone into building battery models, such as the equivalent circuit model, the neural network model, and the electrochemical model. e equivalent circuit model can better respond to the relationship between battery parameters, reflect the dynamic performance of the battery, and facilitate the battery characteristics analysis and parameter identification [26,29]. Here, we propose a second-order RC equivalent circuit model with hysteresis effects. e two RC networks shown in Figure 6 describe the effects of differential polarization and electrochemical polarization, respectively.
Let Uoc(t) be the battery OCV. R0 denotes the ohmic internal resistance of the battery [12]. ere are four parameters in the two RC networks. Re and Ce denote the electrochemical polarization internal resistance and capacitance of the battery, respectively. Rd and Cd denote the concentration polarization resistance and capacitance, respectively. I(t) is the dry circuit current, positive for discharging and negative for charging.
According to KCL and Kirchhoff's Voltage Law (KVL), the ohmic voltage U 0 (t), the electrochemical polarization voltage U e (t), and the concentration polarization voltage U d (t) can be calculated by respectively. And the battery terminal voltage U(t) is By the current integration method, we have Journal of Advanced Transportation where SOC 0 is the initial SOC, Q N is the normal capacity of the battery, and η is the charging and discharging efficiency of the battery.
e system state-space equations are discretized into where τ, τ e and τ d are the sampling periods satisfying Hence, the established discretized state-space equation of the battery system is as follows: where w(k − 1) is the model observation noise. e discretized state output voltage of the model is where v(k − 1) is the observation noise of terminal voltage.

SOC Estimation Based on AUKF.
e key to the UKF is the unscented transform operation to transform the mean and covariance of the nonlinear system, avoiding linearization operations and retaining the high-order terms of the system. e UKF also improves the transmission accuracy of the system Gaussian density. Further, the AUKF iteratively corrects the system noise covariance and the observed noise covariance using maximum likelihood estimation and expectation maximization, resulting in better adaptability and better estimation results [30].
For a nonlinear discrete-time system, the state equation and the measurement equation are as follows: where x k is the system state vector, y k is the measurement vector, u k is the known input vector, w k is the process Gaussian noise, v k is the measurement noise Gaussian, and f(x k , u k ) is a nonlinear measurement function. e AUKF for the battery SOC estimation is illustrated as follows: Step 1: Initialization and state extension where X 0 and P X,0 are the initial state estimate and error covariance matrix. e state vector X k is defined as with the state variables SOC(k), U e (k) and U d (k).
Step 2: 2L + 1 sampling (Sigma) points establishment Step 3: e weight calculation  Journal of Advanced Transportation e calculation of the mean weight and covariance weight can be presented as where λ � α 2 (n + ς) − n is a scale parameter to eliminate the total prediction error, α determines the distribution of sigma points around X and is usually a small positive value ranging from 1 to e − 4 , ς takes values of 0 to 3-n generally, β is used to integrate the X prior estimation and generally selected to be 2, and W (m) i and W (c) i are weighting factors to calculate the mean and covariance of the i-th sigma point, respectively.
Step 4: State estimation time updating Step 5: Covariance matrix time updating where Q k is the covariance of the process Gaussian noise w k . R k is the covariance of measurement noise Gaussian v k , without relationship between them.
Step 6: New sigma points attainment at time k|k-1 Step 7: Measurement estimation Step 8: Kalman gain matrix where Step 9: Residual calculating Step 10: State estimation measurement updating Step 11: Covariance matrix measurement updating e above steps constitute the UKF. e AUKF contains an additional step to adjust the process noise covariance and measurement noise as follows.
Step 12: Adaptive adjustment of Q and R e two noise covariance matrices are updated at each iteration using the following two equations in real time: Journal of Advanced Transportation

Equalization Control Algorithm
When discharged to a low SOC, the battery voltage decreases sharply [18,31]. If the current is high, the battery may be damaged because of staying over-discharging for a long time. Likewise, when the battery is charged to a high SOC, its voltage increases significantly. When charged with a high current, the battery can be overcharged for a long time [32]. Besides, the polarization and ohmic effect are more significant if the battery ages severely, resulting in a more pronounced voltage drop at low SOC and voltage rise at high SOC [33][34][35][36]. us, adopting SOC as the single equalization criterion is not enough; this cannot prevent possible battery damage from overcharging and over-discharging [12,37,38]. Figure 7 is the SOC-OCV characteristic curve of the LIB. Assume that the interval [0.2, 0.8] denotes the SOC value between 0.2 and 0.8, which is considered as the plateau region. e intervals [0, 0.2] and [0.8, 1] are called nonplatform interval where the SOC and OCV are approximately linear, and the terminal voltage can be measured online with a simple monitoring system. However, the OCV has little change in the plateau region. us, the terminal voltage and SOC are both chosen as the equalization parameters in this paper. e SOC-based equalization control algorithm is used when the SOC is in [0.2, 0.8], while the terminal-voltage-based equalization control algorithm is used when the SOC is below 0.2 or above 0.8. Unfortunately, there are various imbalance states; we cannot use the average SOC as an absolute benchmark for the SOC-based equalization algorithm. Figure 8 shows two battery packs in the imbalanced state. e average SOCs of both battery packs are between 0.2 and 0.8. However, in the battery pack shown in Figure 8(a), there is one cell with low SOC and others with high SOC that are at risk of overcharging. In the battery pack shown in Figure 8(b), there is one cell with high SOC and others with low SOC that needs to avoid over-discharging.
us, this paper also proposes the SOC difference as another equalization parameter in the SOC-based equalization control algorithm. Similarly, the terminal-voltage-based equalization algorithm adopts the average and difference of terminal voltage between cells as equalization parameters. e specific implementation flow can be seen in Figure 9 where AFNN is an equalization control algorithm based on equalization parameters. e equalization strategy is developed on the basis of the equalization circuit to optimize the performance of the equalization circuit, so that the overall equalization performance can be maximized [39]. However, controlling the magnitude of the equalization current is a very complex nonlinear control problem. Model neural networks (NNs) can achieve nonlinear mapping with arbitrary accuracy. However, the NN requires a large amount of data to train. In this paper, an adaptive fuzzy neural network is used to control the value of the equalization current in the equalization process. e AFNN algorithm is combined with fuzzy logic control (FLC) and neural network to achieve high selfadaptability and good fault tolerance. e AFNN can adjust the membership function parameters as well as the weights between neurons [40]. In the paper, the AFNN is a firstorder Takagi-Sugeno (T-S) fuzzy neural network based on the hybrid algorithm based on BP and least squares. It requires learning to determine five parameters including the antecedent and posterior parameters. e antecedent parameters of the network are obtained by BP algorithm, and the posterior parameters are identified by least squares, which greatly improves the learning efficiency. e AFNN is divided into five layers, including a fuzzy layer, a fuzzy rule intensity release layer, a rule strength normalization layer, a fuzzy rule output layer, and an output layer, as shown in Figure 10. e AFNN rules are obtained from the expert knowledge during equalization. e expert knowledge improves the reliability of the algorithm [41][42][43].
Layer 1. Fuzzy layer ere are two inputs to the fuzzy layer. For the SOCbased fuzzy neural network, the two inputs are △SOC and SOC avg , which can be expressed as where SOC i is the SOC of the i-th cell among the m cells on the left-hand side of the equalization unit, SOC j is the SOC of the j-th cell among the n cells on the right-hand side of the equalization unit, ∆SOC denotes the difference between the average SOC of the cells on the left-hand side of the equalization unit and the average SOC of the cells on the right-hand sides of the equalization unit, and SOC avg denotes the average SOCs of all cells in the equalization unit. For the terminal-voltage-based fuzzy neural network, the two inputs are the terminal-voltage difference ∆V and the terminal-voltage average V avg , which can be presented as follows: The maximum SOC difference is greater than 0.8 ? Furthermore, the equalization loss [44] of the battery is where E L is the total energy consumption of the battery, E before i is the energy of the i-th battery cell before equalization, E after i denotes the energy of the i-th cell after equalization, and E is the average energy of all battery cells. e number of fuzzy sets of the input parameters determines the number of membership functions in the first layer. e theoretical domain of ∆SOC is 0-0.6, SOC avg is in 0-1, ∆V is in 0 to 1, and V avg is in 2.6-4.2. In terms of the imbalanced state of the battery and characteristics, the theoretical domain of the inputs is divided into five fuzzy sets of very large (VL), large (L), medium (M), small (S), and very small (VS). A fuzzy rule base is developed through expert knowledge of the battery equalization control process and practical experience. Finally, the number of membership functions is obtained. e membership functions selected are all Gaussian functions, denoted as where a is the center of the membership function, b is the width of the membership function, and a and b, as antecedent parameters of the fuzzy neural network, are obtained via database training and learning. e input parameters, ∆SOC/∆V and SOC avg /V avg , are defined as x 1 and x 2 , respectively. e input and output of the first layer are where μ Ai (x 1 ) is i-th membership function of input parameter x 1 , and μ Bj (x) is the j-th membership function of input parameter x 2 .

Layer 2. Fuzzy rule intensity release layer e output value can be calculated by
where ω k represents the activation strength of one of the fuzzy rules.

Layer 3. Rule strength normalization layer
By calculating the weight of the activation strength for each fuzzy rule, the output of the layer is given by Layer 4. Fuzzy rule output layer e output of each fuzzy rule can be expressed as where p k , q k and r k are used as the posterior parameters of the fuzzy neural network and are obtained by training. e layer is used to calculate the output equalization current value by Figure 11, a photograph of the experimental setup and associated instruments, is built as the core of experimental test, and the designing of software and hardware is given. Subsection 5.1 is done in simulation with estimating the parameters in the second-order RC model and assessing the proposed AUKF in estimating the SOC, using the EKF and CKF as benchmarks. Meanwhile, Subsections 5.2 and 5.3 are based on the hardware experimental platform, including a DC supply power, a host computer, an active equalization controller, six serial connected batteries, an equalization circuit board, and an oscilloscope. For the active equalization controller, the MOSFET switch array is used to generate a pair of PWM signal for the MOSFETs to control the equalization circuit [45,46]. e oscilloscope shows the control waveform of the inductors, which can be seen specifically in Figure 5 sawtooth wave, completing the equalization monitoring and characterizing the process of energy transfer. e sensors receive the voltage and current information of the batteries and send them to the host computer. e host computer uses these collected data for SOC estimation, monitoring cell voltage and string temperature, and protecting the whole equalization system [47].

SOC Accuracy Validation.
We aim to estimate five parameters in the second-order RC model, i.e., Re, Ce, Rd, Cd, R0. ey describe the dynamic behavior of the battery. First of all, we use a specific type of the LIB as the experimental object and analyze the Hybrid Pulse Power Characterization (HPPC) of the battery to obtain the pulse discharge current (as shown in Figure 12) and voltage data.
e Parameter Estimation toolbox in MATLAB is then employed to estimate the five parameters. e estimation results conducted on a computer with Intel (R) Core (TM) i7-6700 CPU @ 3.40 GHz 3.41 GHz are shown in Figure 13. With these parameter estimates, a second-order RC equivalent model is built in MATLAB/Simscape. We next compare the AUKF algorithm, the EKF, and the CKF in terms of their accuracy in estimating the SOC. e current values in Figure 12 are used as the inputs for the built equivalent circuit model. Figure 14(a) and Figure 14(b) present the error curves of the three methods. Table 1 summarizes the mean and standard variances of the errors generated by the three methods. We see that the estimation errors of both the EKF and CKF are larger than the estimation error of the AUKF. e AUKF converges faster, and the error tends to 8% in this condition. ere is little doubt that the EKF is simple and suitable for nonlinear systems with a low degree; however, higher order terms of the EKF are ignored, and the filtering accuracy can be immensely reduced. e CKF has high filtering accuracy and good convergence, and yet some of the approximation errors are discarded when estimating the nonlinear system. When it comes down to it, however, the shortcomings of the CKF algorithm may make the filtering fail to meet the proposed consistency, and thus, the state truth cannot be estimated accurately. Sometimes there is also a problem of open-square failure, or even it is scattered when the degree of nonlinearity is high, or the initial error is large. With the advantages of UKF, no linearization error is introduced, and the accuracy can reach the second-order accuracy of Taylor series expansion without calculating Jacobi matrix. However, when the a priori noise statistical properties do not match the actual noise statistical properties, the state estimation performance of the UKF will be poor or even scattered. In the paper, the AUKF can adaptively adjust the process noise variance and measurement noise variance to reduce the model estimation error and suppress the filter divergence [48].

Performance Evaluation of the Proposed MLDIEC.
To analyze the performance of the proposed MLDIEC, we compare it with three other battery equalization circuits: CIEC, PAEC, and DIEC. A comparison between these circuits is carried out in the standing, charging, and discharging states of the battery. e equalization efficiency is measured by two metrics: equalization time and energy loss.
e initial values of SOC are listed in Table 2. e equalization loss of the battery pack is calculated by equation (38). It is significant to note that the energy losses during experiment will be smaller than that in the actual situation for several reasons. For example, line resistance is often Journal of Advanced Transportation neglected. However, this will not affect the magnitude order of energy loss of the four equalization circuits, and thus, the comparisons are still meaningful. Tables 3-5 present the equalization processes of the four equalization circuits in the three states, respectively. e horizontal coordinate is the equalization time, and the vertical one indicates the SOC. e CIEC has cumbersome energy transfer paths and unoptimized equalization units. Hence, its equalization time and energy losses are significantly higher than others. e DIEC adopts the dual parallel method that increases the equalization time by a factor of about one, while the energy can only be transferred between adjacent cells. e PAEC adds a high-level equalization unit to avoid the energy transfer disadvantage of the DIEC. As a result, the equalization time is shorter, and energy losses are lower. e proposed MLDIEC combines the advantages of the PAEC and DIEC. However, it should be noted that because the MLDIEC adopts the dual interleaved inductors that inevitably increase the energy loss from internal resistance of the battery, the energy loss of MLDIEC is slightly higher than that of PAEC. e equalization time and energy loss of the four equalization circuits under the same conditions are given in Figures 15 and 16, respectively. We see that the MLDIEC significantly reduces the energy loss and equalization time at the same time.

Performance Evaluation of the Proposed MLDIEC.
e network model in this paper is constructed in the fuzzy toolbox in MATLAB, and the network design is   completed in three steps: training data import, generation of T-S fuzzy inference system, and learning algorithm selection and training. e generation of the T-S fuzzy inference system and the learning algorithm selection have been described in Section 4. e training data in the network are obtained from the battery characterization and the variation of the battery parameters in the experiment. e values of the antecedent parameters in the network are determined, and the membership functions of the 2 input quantities (△SOC and SOC avg ) are clarified, as shown in Figure 17. Table 6 shows the 25 groups of 75 identification parameters. e switching surface of the AFNN output corresponding to the input is shown in Figure 18.
To test and verify the proposed equalization algorithm-the AFNN-for battery equalization, a comparison is made with the mean-difference algorithm in the standing, charging, and discharging state, as shown in Table 7. Note that, to emphasize the advantages of the AFNN for battery equalization, the differences of initial SOC between cells are set extremely large. We see that the AFNN improves the equalization times by 35.3%, 39.9%, and 37.1% compared with the mean-difference algorithm in the standing, charging, and discharging states, respectively. Meanwhile, the AFNN decreases the equalization energy losses by 4.9%, 4.4%, and 5.3% compared with the mean-difference algorithm in the standing, charging, and discharging states, respectively. e results of the two algorithms are summarized in Figure 19 to facilitate the comparison.      14 Journal of Advanced Transportation

Conclusion
is paper presents an AFNN-based multideck dual interleaved inductor active equalization circuit to reconcile the inconsistency of series-connected LIBs. e circuit provides an optimal path and energy transfer scheme between two nonadjacent cells by a high-level equalization unit. Dual inductors replace the single inductor in the equalization unit, allowing a cell to operate twice in one equalization cycle and avoiding the battery to be idle for a long time. Comparisons with other three equalization circuits show that the proposed equalization structure can greatly accelerate the equalization speed and reduce the equalization loss. e SOC and terminal voltage are chosen as the equalization criterion in different intervals of the SOC-OCV characteristic curve of LIBs, and the AUKF is used for SOC estimation. e AFNN algorithm is employed for effective equalization. Experimental results show that the AFNN algorithm increases the equalization efficiency by about 4.89% and saves the equalization time by about 37.4% compared with the mean-difference algorithm under the same operating conditions. In the future, the battery pack model will be further developed and widely used with more accurate SOC estimation values and less computational burden.

Data Availability
We have presented the data in the form of tables in the paper.  Figure 19: Equalization results based on mean-difference algorithm and AFNN algorithm in the three states.