Journal of Electrical and Computer Engineering

Volume 2014 (2014), Article ID 906537, 8 pages

http://dx.doi.org/10.1155/2014/906537

Research Article

Modelling and Practical Implementation of 2-Coil Wireless Power Transfer Systems

Hong Zhou, Bin Zhu, Wenshan Hu, Zhiwei Liu, and Xingran Gao

Department of Automation, School of Power and Mechanical Engineering, Wuhan University, Wuhan 430072, China

Received 4 April 2014; Revised 8 August 2014; Accepted 21 August 2014; Published 3 September 2014

Academic Editor: Adam Panagos

Copyright © 2014 Hong Zhou et al. This is an open access article distributed under the Creative Commons Attribution License, which permits unrestricted use, distribution, and reproduction in any medium, provided the original work is properly cited.

Abstract.

Wireless power transfer (WPT) based on inductive coupling could be potentially applied in many practical applications. It has attracted a lot of research interests in the last few years. In this paper, the modelling, design, and implementation of a 2-coil WPT system are represented. The prototype system can be implemented using conventional power electronic devices such as MOSFETs with very low costs as it works in relative low frequency range (less than 1 MHz). In order to find out about the optimal working area for the WPT system, the circuit model based on the practical parameters from the prototype is built. The relationships between the exciting frequency, coupling, and output power are analyzed based on the circuit and magnetic principles. Apart from the theoretic study, the detailed implementation of the WPT prototype including the coil design, digital frequency generation, and high frequency power electronics is also introduced in this paper. Experiments are conducted to verify the effectiveness of the circuit analysis. By carefully tuning the circuit parameters, the prototype is able to deliver 20 W power through 2.2 meter distance with 20–30% efficiency.

1. Introduction

Wireless power transfer (WPT) technology can be potentially used in many industrial applications in case that the interconnecting wires are inconvenient, dangerous, or even impossible. It has attracted much of research attention in the last few years. There are several WPT techniques being researched presently. Far-field techniques use propagating electromagnetic waves that transfer energy the same way radios transmit signals but with much bigger transmission power [1]. Inductive coupling (or near-field) techniques operate at distances less than a wavelength of the signal being transmitted, which operates at a relative low frequency comparing with the far-field methods [2].

The early research and analysis of inductive coupling [3, 4] are mainly based on the pure physical theories, which could be difficult for the researchers from electrical engineering background to fully understand. Recent researches [5–7] start to use circuit and magnetic theory to study the fundamental principle of the magnetic resonance coupling, which makes the technology more tangible for a wider range of researchers especially for electrical and electronics engineers.

Potentially, inductive coupling WPT systems can be used in many industrial applications, such as power supplies for moving sensors and transducers [8], medical implants [9, 10], and wireless electric car charging stations [11].

In power industry, due to the importance of high voltage (HV) cables in the transmission network, on-site condition monitoring is a very important issue [12, 13]. However, the power supply is always a major problem for the reliability of the monitoring devices which operate in the harsh outdoor environment with no reliable power sources. Some applications try to use the solar and wind power to solve the problem, but these power sources are not guaranteed in case of continuous bad weather condition which could occur frequently in some places like the mountain areas in South West China.

However, using the WPT technology, a tiny amount of the power can be harvested from the magnetic field around the HV power cables using induction coils and then transferred through the insulator (a few meters distance) to power the monitoring devices installed on the towers, which could be the potential solution for the problem. For this kind of applications, the key requirement is to deliver sufficient power to the load with relative high power transfer efficiency (PTE) and considerable distance. Robustness and reliabilities are also important issues especially for case of the HV cables monitoring.

There are many configurations of WPT system developed recently including the 2-coil [14, 15], 3-coil [16], and 4-coil [17, 18] links. The multicoil structures are able to increase the PTE in some cases, but the price is the increasing complexity of the system structure. Each coil has its own parameters such as resistance, inductance, and capacitance. Some parameters may be sensitive to the external environment like temperature and humidity. More coil loops mean that more tuning work is required to get all the parameters aligned. It could be difficult to maintain the optimal performance in some harsh environment for the practical applications. Balancing the performance, complexity, and reliability, the simple 2-coil structure may be the best option for some industrial applications.

In [14], the optimum design of an inductively coupled 2-coil power transfer system is studied using the conjugate image impendence theory [15]. Theoretically, the optimum parameters of WPT systems can be calculated to maximum power transfer. However, in some applications, it could be difficult or costly to change the intrinsic circuit parameters, which is required by the theory.

In this paper, a WPT solution could be potentially used for HV power cable monitoring is introduced. In order to optimize the working conditions, the circuit models with the practical parameters are analyzed and simulated. Based on the theoretical study, a WPT prototype designed for practical HV power cable monitoring is set up. It is able to deliver 20 W power for a distance of 2.2 m. As it is designed for the practical applications, the resonant frequency is reduced to several hundred kilohertz, which are within the ranges of conventional power electronics components such MOSFETs. It can be easily commercialized as all the power electric components can be purchased with low costs.

2. Circuit and Magnetic Principle of 2-Coil WPT Systems

2.1. Optimal Circuit Model

Figure 1 shows the equivalent circuit model of the 2-coil WPT system using magnetically coupled resonator, where the coil system with self-inductance and , mutual inductance , and copper loss and . As both coils are air core inductors, the iron loss is not considered. Both Tx and Rx coils are connected to the resonant capacitors and . and are the parasitic resistance of and . is the impendence of the AC power source. is the load resistance of the output.

Figure 1: Equivalent circuit model of two-coil WPT system.

For the system shown in Figure 1, the optimal parameters which maximize the wireless power transfer are analyzed in [14]. For a given coil system, the optimal loading capacitance and port impendence are calculated as

where is the sum of and . is the sum of and . Equations (1) and (2) represent the resistance matching condition and (3) and (4) depict the resonance condition. From (3) and (4), it can be seen that in order to maximize the power transmission, the two coils on both sides are required to work at the resonant frequency as

Theoretically, (1)–(4) are able to find out the optimum parameters elegantly. However, in practical applications, as , , and are parasitic values, there is little flexibility for engineers to actually choose circuit parameters for the resistance matching. For a given WPT system, , , , and are fixed values, where it is not possible or convenient to change them.

2.2. Practical Circuit Model

An experimental test rig whose measured circuit parameters are listed in Table 1 is set up in the laboratory. Both Tx and Rx sides have the same inductance and capacitance, so they share the same resonant frequency as required in (5). However, for the resistance part, there is little flexibility for the parameter changes. All the resistance values such as , , , and are the practical measurement from the test rig.

Table 1: Circuit parameters.

Parameter
Value

,
298 uH

,
200 pF

,
2 Ω

2 Ω

,
3 Ω

7 Ω

0.0001 to 0.1

AC voltage
30 V

AC frequency
620 kHz to 680 kHz

Normally the distance between the two coils can be several times of the coil radius, which makes the coupling coefficient a very small value around 0.001 to 0.01. Only a small amount of the flux generated by Tx coil is able to go through the Rx coil. However, a large amount of magnetic energy can still be transferred through the limited amount of flux with relatively high efficiency (around 20 to 30%) when the Rx and Tx coils are in the resonant state. This phenomenon can be explained by the circuit and magnetic theory.

The two-coil model depicted in Figure 1 can be analyzed using Kirchhoff’s voltage law (KVL) as follows:

where

and the is the mutual inductance between Tx and Rx coils. The relationship between the mutual inductance and coupling coefficient is defined as

In order to simplify the the two circuit equations (6) and (7) and are defined as the impendence of both circuit loops as follows:

The two KVL equations (6) and (7) can be solved as

Therefore, the input power which energizes the Tx coil and output power which are consumed on the load can be calculated as

The overall WPT efficiency is

Using data in Table 1, the output power against the exciting frequency and coupling coefficient can be plotted in Figure 2. When the coil distance is small and coupling coefficient between the two coils is big, the WPT works in the over coupled regime as marked in Figure 2. Frequency splitting can be clearly observed as there are two peak output powers. When the coupling between the two coils decreases with the increment of the distance, the system goes into the under coupled regime. The frequency separation between the two peak values decreases until they converge at a single frequency , where is the resonant frequency of both coils [14].

Figure 2: Output power as a function of frequency and coupling coefficient using the parameter given in Table 1.

2.3. Analysis of Practical Parameters

Due to the relative long distance between the two coils, the coupling efficient is very small (0.001 to 0.01). Therefore, can be considered as a close approximation of .

In practical applications, without loss of too much accuracy, technically it can be considered the two-split frequency merged at the resonant frequency when the coupling is as marked in Figure 2. For a practical WPT system with high coils, can be considered as the critical point between the over coupled and under coupled regimes.

For practical system, the circuit parameters for Tx and Rx coils need to be aligned in order to get the maximum WPT power and efficiency, which means that

where and are the angular resonant frequency for the Tx and Rx coils, respectively. The resistance on the Rx side is normally bigger than that on the Tx side as the load resistance is connected in serial with the coil circuits.

From the engineering point of view, can be used as a very close approximation to without inducing big calculation errors. Therefore, the WPT system at resonant frequency can be analyzed to find out the optimal operating area. When , both the power and efficiency against coupling are plotted in Figure 3. It can be seen that the overall efficiency drops when the coupling is decreased. However, the output power increases with the decreasing coupling at the beginning until it reaches the peak value . Then it drops dramatically with the decrease of the coupling.

Figure 3: Output power and efficiency when .

To simplify the analysis, it is assumed that both the Tx and Rx loops have the same inductance and capacitance as and . The resonant frequency for both of the two coils is

When , combining (11), (12), and (15), the output power can be obtained as

In order to get corresponding value of coupling at the maximum power, the derivative of (16) is taken with respect to . By setting the result to zero and solving the equation, is obtained as

For the two coils, their series quality factor is defined as

Combining (17) and (18), the relationship between and the quality factors is

The coupling is roughly reversely proportional to the third power of the coil distance. In order to get the maximum power at long distance, should be as small as possible, which means that factors of both coils are very important parameters for the performance of the WPT. However, high coils are very difficult to make due to the limitation of coil size, material, and so forth. For the case that the distance is several times of the coil diameter, normally the operating area is around the critical point as shown in the shadowed area in Figure 3.

3. Practical Implementation of WPT Systems

There are many existing WPT systems which successfully demonstrated the potential of the new technology in recent years. However, most of them are working with very high frequency around 10 MHz which is far beyond the capacity of the normal switching power electronics such as IGBTs and MOSFETs. Therefore, for a WPT system which can be easily manufactured using the normal power electronic components, the switching frequency must be lower than 1 MHz (for MOSFETs).

3.1. General Structure

Figure 4 is the diagram of the practical application of the proposed WPT system. A DDS (direct digital synthesizer) module AD9850 controlled by a MCU (microcontroller unit) controller is adopted to generate the accurate square wave exciting signal. The frequency signal is amplified by a gate driver module and then drives a MOSFET H-bridge to generate a high frequency AC. The Tx coil is energized by the AC and transmits the power to the Rx coil though the inductive coupling. The high frequency AC is rectified to DC using bridge rectifier on the Rx side. The DC is filtered by capacitors before it drives the load.

Figure 4: Diagram of the practical implementation.

3.2. Coil Design

In order to get a less than 1 MHz resonant frequency for the Tx and Rx coils, both the inductance and capacitance need to be significantly bigger than the high frequency ones. The radius of the two coils is 20 cm. They are winded by 19 turns using Litz cable with 500 strands, which forms inductance of 298 uH.

Low resonant frequency requires bigger capacitance as well as big inductance, which means the parasitic capacitance of the coil winding itself is not big enough and add-on capacitors connected in serial with the winding are necessary. From (12), it is clear that lower capacitance can increase the factor of the circuit and improve the performance of the system. However, capacitors with small capacitance normally induce bigger parasitic resistance, which affects the factor on an opposite way. In some cases, capacitors need to be connected in parallel to get smaller paralytic resistance at the expense of bigger capacitance.

Figure 5 is the circuit model for a practical coil design in which more than one high voltage ceramic capacitor is connected in parallel to decrease the overall parasitic resistance. The overall parasitic resistance is

where is the parasitic resistance for each individual capacitor and the overall capacitance is

Therefore, the factor of the coil can be calculated as

Figure 5: Circuit model for parallel connected capacitors.

For a given type of capacitor, the number of the capacitors needs to be calculated and balanced in order to get the optimal factor. In this case, two 100 pF HV ceramic capacitors are connected in serial to get the best performance. Together with the 298 uH winding inductance, the resonance frequency for both of the two coils is around 642 kHz.

3.3. Frequency Generation

Because of the high factors of the coils, the WPT is very sensitive to the frequency drifting and jigging. A small variation of inciting frequency could result in significant performance drop which can be seen in Figure 2. Conventional analog signal generation cannot meet the precision requirement of the WPT system. Therefore, a digital method based on direct digital synthesizer (DDS) technology is selected as the solution.

A direct digital synthesizer (DDS) module AD9850 controlled by a MCU (microcontroller unit) as shown in Figure 6 is adopted to generate the accurate square wave exciting signal. Using the keyboard on the MCU controller, the output frequency can be tuned from 0.1–1 MHz with the step size of 10 Hz. The output square wave is highly stable compared with the analog circuit due to the explicit advantages of digital frequency generation.

Figure 6: DDS frequency generation with MCU.

3.4. High Frequency Inverter and Rectifier

The coil design makes the whole WPT system switch at 642 kHz which is within the range of Ultra-fast MOSFET. A MOSFET H-bridge is built to amplify the high frequency signal generated by the DDS module and energizes the Tx coil to transmit the electric power.

Assuming the DC input of the inverter is and using Fourier expansion, the square wave AC output put can be represented in infinite serials of the form

where the square wave is transformed into a serial of sinusoidal waves with different aptitudes and frequency.

From Figure 2, it can be seen that only the signals a very narrow band of the frequency are able to pass through the WPT system and the gain for other frequencies is significantly low. The WPT system actually operates like a very sensitive band pass filter. Even though the H-bridge inverter can only generate square waves, only the fundamental frequency is able to go through and other parasitic frequencies are cut off. Therefore, the theoretical analysis based on the AC source is still applicable for the case of H-bridge inverters.

Figure 7 is the picture of the inverter in which four Ultra-fast MOSFET IRF740s forms the H-bridge. The H-bridge is driven by two half-bridge gate driver IR2110. IR2110 has a build-in dead-band of 10 ns. It is expanded to 50 ns to prevent the possible shoot-though because of the high speed switching. On the Rx side, due to the high working frequency, conventional diodes are not fast enough to rectify high frequency AC without inducing significant losses. Therefore, the electric energy received by the coil is rectified to DC by a high speed bridge rectifier made of Shockley diodes. Shockley diodes have very small reverse recovery time (less than 50 ns), which reduces the loss greatly at the high working frequency.

Figure 7: High frequency inverter.

4. Experimental Results

The radius of the both coils is 20 cm and the distance between the two coils is 2.2 m. On the Rx side, a bulb which is selected as the load is illuminated using the energy received from the magnetic resonance as shown in Figure 8.

(a)

(b)

(c)

Figure 8: Picture of the WPT system. (a) Coil structure. (b) Power electronics. (c) Test rig.

The power supply for WPT prototype is a 40V 5A DC power source. The resonant frequencies of the Tx and Rx coils are well matched by adjusting both circuits carefully. The input power, load voltage, and load current are measured. Therefore, both the output power and overall efficiency (with the loss on the power electronics) can be calculated. The experimental results are shown in Table 2. Both the output power and efficiency against the frequency are plotted in Figure 9. It can be seen that high transfer efficiency (more than 20%) can be maintained for a quite wide range from 639 kHz to 645 kHz.

Table 2: Circuit parameters.

Frequency
Load voltage
Load current
Power
Efficiency

638 kHz
6 V
0.83 A
5.0 W
11.2%

639 kHz
10 V
1.39 A
13.9 W
23.8%

640 kHz
11.9 V
1.65 A
19.6 W
26.9%

641 kHz
12.1 V
1.68 A
20.3 W
28.0%

642 kHz
12 V
1.66 A
19.9 W
27.8%

643 kHz
12.1 V
1.68 A
20.3 W
27.5%

644 kHz
11.5 V
1.60 A
18.4 W
26.5%

645 kHz
9 V
1.25 A
11.3 W
22.4%

646 kHz
5.5 V
0.76 A
4.2 W
9.6%

Figure 9: Experimental results.

Because the coupling is bigger than the critical value , the output power does not reach the maximum at the resonant frequency when the resonant frequencies are well aligned. The frequency splitting can be observed clearly as there are two peaks for the output power which are placed on both sides of , which is indicated from the circuit analysis in Section 2.

5. Conclusion and Future Work

In this paper, the circuit modelling and implementation of a practical 2-coil WPT system have been introduced. Using the circuit theory, the relationship between the circuit parameters, coupling coefficient power transfer, and efficiency are analyzed. The optimal working area balancing the efficiency and distance is recommended based on the analysis. In order to verify the WPT proposed circuit theories, a practical WPT prototype is designed and implemented in this paper. The detailed structure of the prototype including the Tx and Rx coils, frequency generation, and high frequency power electronics has also been explained in this paper.

Using the prototype, the WPT experiments at the distance of 2.2 m are conducted. The experiments results show that the WPT prototype can achieve 20 W power transfer at relative high overall efficiency (more than 20%). The voltage splitting phenomenon can be clearly observed as it is predicted from the theoretical analysis.

Since all the components utilized to build the prototype are made of normal electric and electronics components which can be purchased easily from the market with very low costs, there is great potential for the prototype to be commercialized in the future.

Conflict of Interests

The authors declare that there is no conflict of interests regarding the publication of this paper.

Acknowledgment

This research was supported by the National Science Foundation of China under Grant 61374064 and 61304152.

References

A. P. Sample, D. J. Yeager, P. S. Powledge, A. V. Mamishev, and J. R. Smith, “Design of an RFID-based battery-free programmable sensing platform,” IEEE Transactions on Instrumentation and Measurement, vol. 57, no. 11, pp. 2608–2615, 2008.

A. Kurs, A. Karalis, R. Moffatt, J. D. Joannopoulos, P. Fisher, and M. Soljacic, “Wireless power transfer via strongly coupled magnetic resonances,” Science, vol. 317, no. 5834, pp. 83–86, 2007.

A. Karalis, J. D. Joannopoulos, and M. Soljačić, “Efficient wireless non-radiative mid-range energy transfer,” Annals of Physics, vol. 323, no. 1, pp. 34–48, 2008.

R. E. Hamam, A. Karalis, J. D. Joannopoulos, and M. Soljačić, “Efficient weakly-radiative wireless energy transfer: an EIT-like approach,” Annals of Physics, vol. 324, no. 8, pp. 1783–1795, 2009.

Z. N. Low, R. A. Chinga, R. Tseng, and J. Lin, “Design and test of a high-power high-efficiency loosely coupled planar wireless power transfer system,” IEEE Transactions on Industrial Electronics, vol. 56, no. 5, pp. 1801–1812, 2009.

L. Chen, S. Liu, Y. C. Zhou, and T. J. Cui, “An optimizable circuit structure for high-efficiency wireless power transfer,” IEEE Transactions on Industrial Electronics, vol. 60, no. 1, pp. 339–349, 2013.

M. Kiani and M. Ghovanloo, “The circuit theory behind coupled-mode magnetic resonance-based wireless power transmission,” IEEE Transactions on Circuits and Systems. I. Regular Papers, vol. 59, no. 9, pp. 2065–2074, 2012.

J. de Boeij, E. Lomonova, J. L. Duarte, and A. J. A. Vandenput, “Contactless power supply for moving sensors and actuators in high-precision mechatronic systems with long-stroke power transfer capability in x-y plane,” Sensors and Actuators A: Physical, vol. 148, no. 1, pp. 319–328, 2008.

P. Li and R. Bashirullah, “A wireless power interface for rechargeable battery operated medical implants,” IEEE Transactions on Circuits and Systems II: Express Briefs, vol. 54, no. 10, pp. 912–916, 2007.

P. Si, A. P. Hu, S. Malpas, and D. Budgett, “A frequency control method for regulating wireless power to implantable devices,” IEEE Transactions on Biomedical Circuits and Systems, vol. 2, no. 1, pp. 22–29, 2008.

J. L. Villa, J. Sallán, A. Llombart, and J. F. Sanz, “Design of a high frequency inductively coupled power transfer system for electric vehicle battery charge,” Applied Energy, vol. 86, no. 3, pp. 355–363, 2009.

S. Jones, G. Bucea, A. McAlpine et al., “Condition monitoring system for TransGrid 330kV power cable,” in Proceedings of the International Conference on Power System Technology (POWERCON '04), pp. 1282–1287, Singapore, November 2004.

E. Gulski, P. Cichecki, J. J. Smit, P. P. Seitz, B. Quak, and F. de Vries, “On-site condition monitoring of HV power cables up to 150kV,” in Proceedings of the International Conference on Condition Monitoring and Diagnosis (CMD ’08), pp. 1199–1202, April 2008.

N. Inagaki, “Theory of image impendence matching for inductively coupled power transfer systems,” IEEE Transactions on Microwave Theory and Techniques, vol. 62, pp. 901–908, 2014.

R. Roberts, “Conjugate-image impendences,” Proceeding of the IRE, vol. 34, no. 4, pp. 198–204, 1946.

M. Kiani, U.-M. Jow, and M. Ghovanloo, “Design and optimization of a 3-coil inductive link for efficient wireless power transmission,” IEEE Transactions on Biomedical Circuits and Systems, vol. 5, no. 6, pp. 579–591, 2011.

A. P. Sample, D. A. Meyer, and J. R. Smith, “Analysis, experimental results, and range adaptation of magnetically coupled resonators for wireless power transfer,” IEEE Transactions on Industrial Electronics, vol. 58, no. 2, pp. 544–554, 2011.

T. C. Beh, M. Kato, T. Imura, S. Oh, and Y. Hori, “Automated impedance matching system for robust wireless power transfer via magnetic resonance coupling,” IEEE Transactions on Industrial Electronics, vol. 60, no. 9, pp. 3689–3698, 2013.