Joint Transceiver Optimization of MIMO SWIPT Systems Assisted by Reconfigurable Intelligent Surface

. In this work, a reconﬁgurable intelligent surface (RIS)-assisted multiple-input multiple-output (MIMO) system is studied with wireless energy harvesting (EH). Speciﬁcally, we focus on maximizing the harvested power at the receiver by joint optimization of the signal covariance, the phase shifter, and the power splitting factor, subject to the information rate and transmit power constraints. The formulated problem is hard to address due to the nonconcave objective and the nonconvex constraints. To tackle these challenges, an alternating optimization (AO) framework is proposed, where the phase shifter is solved by the penalty-based method. Simulation results validate the performance of the proposed approach.


Introduction
Recently, the reconfigurable intelligent surface (RIS) has been treated as a promising technique for wireless networks, due to the low cost and energy-efficient merits [1]. Specifically, the authors of [2,3] studied the RIS-assisted multipleinput single-output (MISO) network and multiple-input multiple-output (MIMO) network, respectively, which suggested that joint active beamforming (BF) and phase shifter (passive BF) design can improve the performance of wireless networks. en, the work in [4] studied the joint active and passive BF design in RIS-aided wiretap wireless channels, which demonstrated the ability of RIS in improving the security of wireless networks.
Besides the effect of improving the spectrum efficiency or expanding the coverage in wireless networks, the application of RIS is also appealing for other application scenarios such as wireless location and radar signal detection. Specifically, the work in [5] studied the near-field passive localization and gain-phase compensation with partly calibrated array. Also, the study in [6] investigated the three-dimensional near-field localization using a spatially spread acoustic vector sensor.
en, the authors of [7,8] studied the joint location and communication design in RIS-aided wireless networks. As for the radar signal detection, in [9], an estimation algorithm for MIMO radar was developed with arbitrary sensor geometry. Also, in [10], the authors proposed a generalized multiple signal classification (MUSIC)-like algorithm for a height measurement with meter wave polarimetric radar. en, in [11,12], the authors investigated the algorithm design in the RIS-aided radar system, which suggested that RIS can improve the performance of radar target detection. Furthermore, in [13], the authors proposed dual-polarized RIS schemes in MIMO network, which suggested that dualpolarized RIS can further improve the spectrum efficiency in the MIMO network. Besides these works being mainly based on far-field behaviors of RIS, recently in [14], the authors studied the near-field behaviors of RIS and proposed power scaling laws. ese works suggest the various application perspectives of RIS.
On the other hand, wireless energy harvesting (EH) has been regarded as an effective approach to improve the energy efficiency (EE) of wireless networks, where EH-enabled wireless devices can harvest energy from either radio frequency (RF) signals radiated by the transmitter (Tx) and recharge their batteries, which is commonly named as simultaneous wireless information and power transfer (SWIPT) [15,16].
Specifically, the authors of [15,17] studied the SWIPT design with power splitting (PS) and time switching (TS) schemes, respectively. However, the study in [18] investigated the hybrid PS and TS design in the full-duplex MIMO SWIPT channel. Currently, SWIPT has been widely used in various wireless networks such as the wireless sensor network (WSN) [19] and the Internet-of-ings (IoT) network [16].
Moreover, several works investigated the effect of RIS in improving the information and energy transfer in SWIPT work. Specifically, by assuming the individual information receiver (IR) and energy receiver (ER), in [20,21], the authors investigated the RIS-assisted MISO and MIMO network with SWIPT, where penalty dual decomposition (PDD) and alternating optimization (AO) methods were proposed, respectively. en, in [22], the authors studied the co-located receiver design in RIS-assisted SWIPT network, where a penalty-based majorization-minimization approach was proposed to optimize the information rate under the EH constraint. Also, the authors of [23] studied the secrecy SWIPT design with the assistance of RIS, where a penaltybased manifold optimization was proposed.
e aforementioned works about SWIPT network mainly focused on the transmission power minimization or information rate maximization design. In fact, maximizing the harvested power is another kind of objective, which has been less investigated in RIS-assisted SWIPT systems. Motivated by these observations, this work considers a MIMO SWIPT system where a Tx sends information and energy to a receiver (Rx), with the aid of a RIS. To be specific, we study a joint signal covariance, RIS passive BF, and Rx PS ratio design to maximize the harvested power, subject to the information rate constraint and the power budget. e formulated problem is hard to tackle, since the objective is nonconcave and the constraints are nonconvex. To address these challenges, an alternating optimization framework is proposed, where the phase shifter is solved by the penaltybased semidefinite relaxation (SDR) method. Simulation results validate that with proper designed passive BF, RIS can significantly enhance the harvested power at Rx.
Notations. roughout this work, boldface lowercase and uppercase letters denote vectors and matrices, respectively. e superscripts T, * , and H denote the transpose, conjugate, and conjugate transpose, respectively. Diag(a 1 , . . . , a N ) is a diagonal matrix with diagonal elements a 1 , . . . , a N , while diag(A) denotes a vector consists of the main diagonal elements of A, respectively. Tr(·) and rank(·) represent the trace and rank. Besides, R · { } denotes the real part of a complex variable. A ± 0 indicates that A is positive semidefinite. ⊙ is the Hadamard product. I is an identity matrix with proper dimension. CN(u, Σ) denotes a circularly symmetric complex Gaussian random vector with mean u and covariance Σ. | · | denotes the absolute value or the determinant. In addition, ln(·) denotes the natural logarithm.

System Model.
We study a RIS-aided MIMO system as illustrated in Figure 1, which have one Tx, one RIS, and one Rx. It is assumed that Tx and Rx are equipped with N T and N R antennas, while the RIS has M reflecting elements, respectively. e channel coefficients between Tx to Rx, Tx to RIS, and RIS to Rx are denoted as H ∈ C N R ×N T , F ∈ C M×N T , and G ∈ C N R ×M , respectively.
Let s ∼ CN(0, Σ) denotes the transmit signal with Σ ∈ C N T ×N T being the covariance. en, the received signal at the Rx is where n r ∈ C N R ×1 is the noise vectors at Rx with n r ∼ CN(0, σ 2 r I). e phase shifter matrix of the RIS is denoted by Θ � Diag(θ 1 , . . . , θ m ), with θ m denoting the reflecting coefficient (RC) of the m-th element satisfying |θ m | 2 � 1.
Rx utilizes a PS ratio ρ to divide the received signal into two streams, which is given by where n p ∈ C N R ×1 is the processing noise at Rx with n p ∼ CN(0, σ 2 p I). us, the harvest energy at Rx is given by where H ∧ � H + GΘF is the equivalent channel from Tx to Rx, and we assume the unit energy conversion efficiency at the Rx.
Accordingly, the information rate is

Problem Formulation.
We aim to maximize the harvested power by jointly designing the transmit signal, the RC, and the PS ratio. To be specific, the problem is formulated as follows: where η is the information rate threshold and P s is the maximum power for Tx. For any given Σ, Θ { }, η achieves the maximum when ρ � 0. us, (5a) is feasible when the optimal value of the following problem is no less than η: However, since E(Σ, Θ, ρ) and R(Σ, Θ, ρ) are nonconcave, (5) is nonconvex and hard to address. In the rest part, we assume that (5) is feasible and solve (5).

An AO-Based Method for Problem (5)
First, we define σ 2 ≜ σ 2 r + σ 2 p , ω 2 ≜ σ 2 r N T /σ 2 , and H � H ∧ /σ. Since ρσ 2 r is commonly much smaller than σ 2 p , we omit this term in the rate expression and obtain the following problem: It should be noted that, with fixed Σ, Θ { }, (7) is convex with respect to (w.r.t.) ρ. In addition, with fixed ρ, Θ , (7) is convex w.r.t. Σ. Both the two subproblems can be solved by the toolbox CVX [24]. e main difficulty in (7a) is the optimization of Θ, since the unit modulus constraint (UMC) for Θ is nonconvex. Firstly, according to [15], solving (7) To further transform (8), we introduce the following lemma.

Via Lemma 1, we have Tr(GΘFΣF H
Here, we develop the penalty-SDR method to solve the phase shifter design. To be specific, we introduce slack variable X � xx H , which means that X ± 0 and rank(X) � 1. us, we attain en, we handle the nonconvex (11c), where the following lemma is utilized.
However, ln|I + X| is concave w.r.t. X. To handle this term, a penalty method is used by adding this term into (11). en, (11) can be rewritten as where κ is a penalty factor to penalize any violation of rank(X) � 1. Moreover, ln|I + X| is concave w.r.t. X and thus can be upper bounded as ln|I + X| ≤ Tr I + X n − 1 X − X n + ln I + X n . (14) Based on (13), (14) can be written as is convex w.r.t. X and hence it can be efficiently solved by CVX. A rank-one X * can be obtained by solving (15) for a sufficiently small κ, and x * can be attained by the eigendecomposition of X * . Besides, it is easily known that any rotation of x * is also the optimal solution of (11). us, we rotate x * by an angle − α, where α is the phase of the last Mathematical Problems in Engineering element of x * . Via this operation, we can obtain the optimal x * , where the last element is set to 1 and the rest elements constitute the vector θ * .
In addition, we assume that the Tx-Rx link follows the Rayleigh fading, while the cascaded link follows the Rician fading with Rician factors 2.5 and 4, respectively. e coordinate of Tx, RIS, and Rx are set as (0, 5), (50, 5), and (50, 0), respectively. Here, we compare the design with the following methods: (1) fixed PS ratio method, e.g., set the fixed ρ � 0.5; (2) the random RIS method, e.g., choose the reflecting coefficient randomly; (3) the no RIS scheme. ese methods are labeled as "Proposed method," "Fixed PS ratio," "Random RIS," and "No RIS," respectively. First, Figure 2 plots the harvested power versus P s , where we can see that the harvested power increases with P s for all these schemes. e proposed method achieves the best performance among these methods, while no RIS-assisted method suffers the worst performance. In addition, the fixed PS ratio design achieves better performance than random RIS design. en, Figure 3 shows the harvested power versus M, where we can see that with the increment of M, the harvested power increases for all these methods. However, our proposed design always obtains more harvested power than the other schemes, since with larger M, more signals can arrived at the RIS and the signals arrived at the Rx will increase, provided that the phase shifts are appropriately optimized.

Conclusion
is work handled the joint design in a RIS-assisted MIMO system with SWIPT, where an AO algorithm has been proposed to maximize the harvested power and the phase shifter is solved by the penalty-based SDR method. Simulation results validated the ability of RIS in improving the wireless EH ability.

Data Availability
Data are available on request to the corresponding author.

Conflicts of Interest
e authors declare that there are no conflicts of interest regarding the publication of this article.