Suppression of Thrust Fluctuation of a New Ironless Tubular Permanent Magnet Synchronous Linear Motor Based on the Halbach Array

,e air gap magnetic field (AGMF) is the key factor in determining the ironless tubular permanent magnet synchronous linear motor (ITPMSLM). ,e distortion of its waveform causes thrust fluctuation during the operation of the motor, resulting in poor machining accuracy of the machine tool. To solve this problem, this paper proposes a new chamfered permanent magnet structure (CPMS) to improve its performance. First, the equivalent magnetic charge method is used to analyze the AGMF, and the analytical expressions of the no-load back EMF and thrust of the new motor are obtained. Second, the AGMF of six kinds of CPMS is analyzed by the Fourier coefficient. Taking the minimum harmonic distortion rate as the optimization objective, the CPMS that makes the AGMFwaveform reach the best sinusoidal property is obtained and the no-load back EMF and thrust of the newmotor are analyzed. ,en, the new motor is compared with the ITPMSLM of rectangle permanent magnet structures (RPMS). Finally, according to the CPMS, the test prototype is built and tested under different working conditions. ,e research results show that when the outer circumference is 45 chamfered, the ratio of permanent magnet thickness h2 to the chamfered thickness h1 is 0.8; the sinusoidal property of AGMF is the best, and this structure can effectively reduce the motor thrust fluctuation rates to less than 0.01%, which verifies the effectiveness of the CPMS in improving the sinusoidal property in the AGMF and restraining the thrust fluctuation of the ITPMLSM.


Introduction
e tubular permanent magnet synchronous linear motor (TPMSLM) has the advantages of a simple structure, high utilization rate of the primary winding, no lateral end effect, and easy adjustment and control. It is widely used in highprecision fields such as laser cutting machines [1]. However, with the existence of thrust fluctuation, the motor will produce noise, vibration, and other problems that seriously affect its operating characteristics and reduce machining accuracy [2,3]. erefore, it is of great theoretical and practical significance to carry out research on thrust fluctuation suppression of TPMSLM. e method of different pole groove matching and the oblique pole are used to weaken the magnetic resistance, which can effectively reduce the thrust fluctuation of the motor [4]. e magnetic resistance of the permanent magnet linear synchronous motor is studied by the numerical calculation method. It is proposed that the thrust fluctuation can be minimized by changing the end tooth structure and magnetic pole shape; the cogging magnetic resistance can also be weakened [5][6][7][8].
e relationship between the minimum end force and the primary length is derived; then, the end magnetic resistance is studied by changing the primary length. On the basis of the optimal primary length, the thrust fluctuation is restrained by using the theory of a magnetic separation ring [9]. e integral structure of the auxiliary pole is adopted to weaken the thrust fluctuation. e primary core is connected with the additional auxiliary pole by a magnetic isolation bridge, which can effectively eliminate the source of error and improve the mechanical strength of the motor [10]. A study proposed a double mover bilateral Halbach permanent magnet array linear motor that reduces the motor thrust fluctuation by optimizing the motor magnetic pole structure and improving the motor magnetic energy density [11]. Another study proposed a Halbach alternating pole structure by adding two tangential magnetized permanent magnets in the alternating pole structure that can reduce the interpole flux leakage and increase the air gap flux density. is structure helps reduce the thrust fluctuation of motor [12]. e studies used the v-coil and an equivalent magnetization method to analyze the model and a genetic algorithm to locally optimize the motor design and finally obtained a motor model with minimum local thrust fluctuation [13]. Although these studies have effectively weakened the motor thrust fluctuation, the thrust amplitude is also significantly reduced.
Studies used the equivalent magnetization method to solve the electromagnetic field of the motor, which deduces the analytical property of magnetic density, back EMF, and inductance and proposes an improved TPMSLM [14][15][16]. However, the sinusoidal property of the AGMF in these studies is poor, and the thrust fluctuation is unstudied. A study analyzed TPMSLM with axial and radial magnetization structure by using the method of the equivalent magnetic circuit and equivalent magnetization, respectively; analyzed the influence of several main parameters of the motors on the magnetic field; and obtained the analytical calculation of AGMF intensity and the thrust of TPMSLM. However, this is too complex and inaccurate [17,18]. Another study calculated the TPMSLM thrust based on the relationship between the back EMF and thrust, but the calculation of thrust fluctuation suppression was not described [19]. Other studies analyzed the magnetic field of axially magnetized TPMSLM with an analytical method but did not analyze the influence of structural parameters on AGMF, especially thrust fluctuation [20,21]. e magnetic pole offset method was used to weaken the cogging force of TPMSLM and give the calculation of the magnetic pole offset, but it is difficult to use this method for the axial magnetization structure of TPMSLM [22,23]. Although these studies can achieve the purpose of restraining thrust fluctuation, the main disadvantages are that the structural complexity is increased and the manufacturing cost is greatly increased [24,25]. A TPMSLM with axial magnetization has been designed, and the influence of motor size on performance has been analyzed in detail [26,27]. Studies conducted an in-depth analysis on the cogging force and eddy current loss of TPMSLM and suppressed the thrust fluctuation through the optimal design of the motor [28,29]. A study proposed a primary TPMSLM with flux switching. e motor uses a magnetic isolation bridge to solve the problem of an asymmetric magnetic circuit of end armature winding and suppress thrust fluctuation [30]. However, the primary structure of the motor is complex and difficult to manufacture. Another study proposed a flux reversal primary TPMSLM, which is relatively simple to manufacture, but the motor is a single-phase motor with a large thrust fluctuation and self-starting problems and is not suitable for longdistance drive system applications [31]. In addition, there are usually three common permanent magnet structures in TPMSLM: a radial magnetization structure, an axial magnetization structure, and a Halbach structure [32]. To enhance the main magnetic field, the stator generally adopts a Halbach array [33].
To sum up, most of the methods to weaken the thrust fluctuation of a TPMSLM are for a TPMSLM with an iron core, and there are few studies on restraining the thrust fluctuation of an ironless tubular permanent magnet synchronous linear motor (ITPMSLM). e AGMF is the key problem in determining the thrust performance of the ITPMSLM, and its waveform distortion is the key factor in producing thrust fluctuation during the operation of an ITPMSLM. erefore, with a CPMS, the minimum harmonic distortion rate of the AGMF waveform as the optimization objective is proposed to suppress the thrust fluctuation of an ITPMSLM. First, the AGMF distribution, no-load back EMF, and thrust of the motor are calculated based on the equivalent magnetic charge method. Second, the AGMF with six different CPMS kinds is analyzed, and the CPMS that makes the AGMF waveform reach the best sinusoidal property is obtained. e no-load back EMF waveform distortion rate and thrust harmonic content of the new motor are analyzed by an analytical method. en, the analytical method is verified by a finite element method. Finally, combined with the above scheme, the no-load back EMF and the thrust fluctuation of the new motor are tested to verify the feasibility and effectiveness of the CPMS in improving the sinusoidal property of the AGMF and restraining the thrust fluctuation of the motor.

Topology Design of New ITPMSLM with CPMS of Halbach Array
e ITPMSLM includes a stator and mover, and its topology is shown in Figure 1. e permanent magnet ring is a Halbach array fixed on the stainless steel back yoke through a special installation process to form the stator, so as to ensure that there will be no relative movement between the stator's permanent magnet ring and the back yoke when the motor works. e winding is encapsulated with special insulating materials such as epoxy resin and forms a mover with the yoke. e winding distribution is as follows: A+, A−; B+, B−; C+, C−. e mover is lightweight and has a fast speed response, and there is no influence of cogging and end breaking, so there is no cogging effect or end effect. e area formed between the stator and the mover is called the air gap area. To obtain a large thrust and not to affect the movement of the mover, the smaller the air gap area, the better. Figure 2 shows that after the RPMS of the Halbach array is magnetized, the magnetic lines of the AGMF near the direct contact of the two magnets are distorted greatly and change unevenly, which will increase the thrust fluctuation of the motor. A CPMS is proposed to solve these problems. e permanent magnet is a circular cylinder and chamfered on both sides of the outer circumference. As shown in Figure 3, near the direct contact of the two magnets, the distortion of the magnetic line of force of the AGMF is reduced, and the variation is more uniform through the CPMS, which will reduce the motor's thrust fluctuation.

Model Establishment of the New Motor
During the motor operation, the AGMF of the ITPMLSM is a variable vector with size and direction; according to the motor structure, it is divided into the radial component and the axial component, and the AGMF density of the radial component is the main source of motor thrust. erefore, this section first calculates the analytical model of radial AGMF density [34] and then calculates the analytical model of the no-load back EMF and thrust of the ITPMSLM with CPMS of the Halbach array (hereinafter referred to as the new motor).

Building the Analytical Model for the AGMF.
e CPMS constituting the stator of the new motor in Figure 1 is completely symmetrically distributed along the central axis in space, and the magnetic charges density on the upper, lower, left, and right surfaces is M. Now, take the CPMS magnetized along the +x direction as an example, and the magnetic field analytical model is as shown in Figure 4.
Before building the analytical model of AGMF, make the following assumptions: (1) e length of the motor stator is infinite (2) e permeability of the motor back yoke is infinite (3) e permanent magnet is uniformly magnetized without demagnetization e magnetic field is a static magnetic field, and the magnetic charge equation can be obtained by where M is the surface magnetic charge density of permanent magnet, unit: A/m 2 . Moreover, the scalar ϕ m1 can be obtained from (1): (2) In Figure 4, r is the radius of the permanent magnet; ρ′ and φ′ are the coordinates of the magnetic charge point in the source area; ρ and φ are the coordinates of the field point; the position vector of the field point is x; and x′ is the position vector of the source point. For |x − x′| −1 , use the integral transformation in [26] and the properties of the Bessel function of imaginary argument [27] to calculate the gradient of the ϕ m1 , and the radial flux density of +x magnetization can be obtained as follows: dk cos(kz)K 1 (kρ)rI 1 (kr). (3) Similarly, the radial flux densities of the three sides magnetized in the −x, +y, and −y directions can be calculated as follows: Because the motor stator is composed of n permanent magnets, using the superposition principle, the magnetic density of the AGMF of the motor can be obtained as follows:    Shock and Vibration

Building the Analytical Model for No-Load Back EMF and rust.
e winding coil of the new motor is surrounding the stator in an axisymmetric manner, and each phase winding is formed by several groups of coils in series. Figure 5 is a schematic diagram of the winding, where R S is the outer radius of the winding, R S1 is the inner radius of the winding, t w is the axial width of the winding, and h w represents the thickness of the winding.
According to Faraday's law of electromagnetic induction, when the mover moves in a straight line along the Z axis, the radial magnetic field will be cut in each ring coil to produce a no-load back EMF. e no-load back EMF generated in each coil is derived according to (5), and then the no-load back EMF of the same phase coil can be added to obtain the noload total back EMF. However, the calculation process is complex and time-consuming. To simplify the calculation, it can be assumed that all coils are concentrated at the average radius. As shown in Figure 5, if the position of the axis of a group of coils is Z, the average magnetic density of the radial AGMF in the coil area of the group is the following: e no-load back EMF of this group of coils at this position is the following: In (7), N is the number of winding turns and L av is the average length of coil per turn. Using the above assumptions, it is considered that the coils are concentrated at the average magnetic density, and the thrust of a group of coils can be obtained as follows: I (z) is the alternating current input to the winding. e total motor thrust can be obtained by adding the thrust to all coil groups. e thrust fluctuation rate is taken as the thrust fluctuation analysis index and is defined as where F max is the maximum thrust value in the stroke, F min is the minimum thrust value in the stroke, and F avg is the average thrust in the stroke. e thrust fluctuation rate can reflect the stability of thrust during motor operation. e smaller the thrust fluctuation rate, the more stable the motor operation (i.e., the smaller the thrust fluctuation).

Analysis of AGMF.
Because the sinusoidal waveform of radial AGMF is the key problem of motor thrust fluctuation, the analytical model of AGMF of the different CPMS will be analyzed in this section, and the optimal sinusoidal radial AGMF waveform will be determined in combination with the total harmonic distortion rate of the radial AGMF waveform. e new motor design is symmetrical along the central axis, so it can take the half-plane simplified into a two-dimensional plane for research, as shown in the physical model of CPMS in Figure 6. e chamfer here is 45°chamfer along the outer circumference. When the polar distance and thickness h 2 of the CPMS are determined, the different chamfered thickness h 1 is selected to calculate the radial AGMF at different h 1 /h 2 . Take the magnetic induction intensity of radial AGMF at r � 15 mm for analysis, and the results are shown in Figure 7.
Fourier analysis of the radial AGMF at different h 1 /h 2 in Figure 7 will obtain the fundamental wave and harmonic content, as shown in Figure 8.
To unify the standard to measure the sinusoidal nature of the waveform, the total harmonic distortion rate (THD) of radial AGMF is defined as its evaluation index. e THD is It can be seen from Figure 8 that as h 1 /h 2 becomes smaller, the fundamental amplitude of the radial AGMF also gradually decreases. e higher the h 1 /h 2 is, the larger the chamfer and the smaller the radial AGMF induction intensity are. To compare the performance of CPMS at different h 1 /h 2 , the total harmonic distortion rate of radial AGMF under corresponding conditions is calculated, as shown in Table 1. Table 1 shows that the smaller the THD, the smaller the harmonic components of the reflected waveform and the better the sine of the waveform. rough the comparative analysis of magnetic density harmonics and distortion rate of radial AGMF under six structures when h 1 /h 2 � 0.8, the amplitude of radial AGMF density waveform is relatively high and the waveform distortion rate is low. erefore, the CPMS in this paper can effectively improve the sinusoidal characteristic of the radial AGMF waveform and achieve the best result.

Analysis of No-Load Back EMF.
According to the above analysis, the sinusoidal waveform of the radial AGMF is best when h 1 /h 2 � 0.8. Based on this, the no-load back EMF  (7), and the three-phase no-load back EMF waveform and harmonic content obtained by the analytical model are analyzed (see Figures 9 and 10). By building the no-load back EMF model of the new motor, the no-load back EMF of the motor when v � 0.02 m/ s and v � 1 m/s are calculated, and results of the numerical method are compared with those of the analytical method (see Figures 9 and 10). Figures 9 and 10 show that when the new motor operates at v � 0.02 m/s and v � 1 m/s, the no-load back EMF has a good sinusoidal performance, and only a few fifth harmonics exist in each harmonic component of the no-load back EMF, which shows that the no-load back EMF harmonic of the new motor can be effectively suppressed by using the CPMS on the premise of ensuring the sinusoidal waveform of the radial AGMF. It provides a strong basis for the subsequent analysis of the thrust and thrust fluctuation analytical model.

Analysis of rust.
e AGMF is the key problem of the motor thrust. Equation (8) is derived from (6) assuming that the winding radii of all coils are concentrated at the average radius. erefore, to verify the effectiveness and correctness of the CPMS, this paper establishes the thrust analytical model of the new motor when I (z) � 1.3 A (see Table 3 for the new motor parameters); the thrust waveform and harmonic content of the new motor are obtained by the analytical model as shown in Figure 11. Figure 11 shows that the thrust of the new motor is sinusoidal, but there are still harmonics that cause thrust fluctuation. To determine the harmonic times and content, we calculate the harmonic components in thrust through Fourier analysis (see Table 2). Table 2 shows that, in addition to the DC component, there are multiple harmonic components of the sixth in the thrust, and the harmonic content of other times is almost zero. erefore, the motor thrust can be expressed as the sum of the DC component and multiple harmonic components of 6th; that is, Equation (11) can be further simplified. In the multiple harmonic components of the sixth, except for the sixth harmonic, the sum of other harmonic contents is less than 0.1% of the total thrust, which can be simplified as us, the sum of each harmonic of the thrust of the new motor accounts for 0.67% of the total thrust of the motor, and the distortion rate of the thrust waveform is less than 0.01%. e analytical results of the thrust show that the CPMS can effectively suppress the thrust fluctuation caused by the distortion of the radial AGMF waveform of the ITPMSLM and stabilize the thrust output of the motor.   h1/h2=1 h1/h2=0.9 h1/h2=0.8 h1/h2=0.7 h1/h2=0.6 h1/h2=0.5

Finite Element Verification of AGMF.
e above analytical model of the new motor is analyzed. To further verify the correctness of the CPMS in reducing the distortion rate of the AGMF waveform and restraining thrust fluctuation, this section makes a finite element comparative analysis between the new motor and the ITPMSLM with the RPMS of the Halbach array. It should be noted that except for the different shapes of permanent magnets (the pole distance and thickness of permanent magnets are the same), the motor structure parameters of the ITPMSLM with RPMS of the Halbach array are consistent with those of the new motor (see Table 3). Figures 12 and 13 show the finite element analysis cloud diagrams of magnetic flux density of the magnetized magnetic field of the ITPMSLM of the CPMS and RPMS of the Halbach array. Figures 14 and 15 are the magnetic line finite element analysis cloud diagrams of the magnetizing magnetic field of the ITPMSLM with the CPMS and RPMS of the Halbach array.
According to the finite element analysis of Figures 12 and  13, the magnetic flux density of the RPMS excitation magnetic field at the interface of the permanent magnet is enhanced, resulting in the large distortion of the magnetic line in the process of forming the loop (as shown in Figure 15), resulting in poor sinusoidal characteristics of the radial AGMF. However, the flux density of the CPMS at the interface of the permanent magnet is evenly distributed, and the closed-loop distortion of the magnetic line is very small (as shown in Figure 14), which makes the radial AGMF sinusoidal.
According to the above analysis, the magnetic density of the radial AGMF center of the excitation magnetic field composed of two magnetic pole structures at r � 15 mm is selected for the finite element comparative analysis. e calculation results are shown in Figure 16. Figure 16 shows that the finite element result of the radial AGMF center magnetic induction intensity of the RPMS has an error of 3.2% in the distribution of the standard   sinusoidal function 1, whereas the finite element result of the radial AGMF center magnetic density of the CPMS basically fits with the standard sinusoidal function 2. e results show the radial AGMF magnetic field produced by the CPMS has better sinusoidal and harmonic content and is less than that of the RPMS.

Finite Element Verification of No-Load Back EMF.
e distortion of the AGMF waveform has a great influence on the waveform of no-load back EMF. erefore, in this paper, the no-load back EMF generated in the three-phase winding when the mover of the ITPMSLM with CPMS of the Halbach array of the CPMS and the RPMS moves at        Figure 17.
Because of the symmetrical structure of the motor, there are no even harmonics in the no-load back EMF. Take the phase A no-load back EMF waveform in Figure 17 for Fourier analysis and obtain the fundamental wave, higher harmonic content, and total harmonic distortion rate of phase A no-load back EMF of the two magnetic pole structures (see Table 4). Table 4 shows that by comparing the no-load back EMF of the two motors through the finite element method, the harmonic distortion rates at v � 0.02 m/s and v � 1 m/s are 0.43%, 0.33%, 0.23%, and 0.21%, respectively. at is, the total harmonic distortion rate of the no-load back EMF of the new motor is lower, and it is verified that the CPMS can improve the sinusoidal nature of the radial AGMF.

Finite Element Verification of rust.
To verify the effectiveness of the CPMS in restraining the thrust fluctuation of the ITPMSLM, the thrust models of the CPMS and RPMS are compared by the finite element method, and the thrust distribution curves under the two permanent magnet structures are obtained, as shown in Figure 18.
According to the above finite element results and in combination with (9), the thrust fluctuation rates of the ITPMSLM with CPMS and RPMS of the Halbach array are 0.01191 and 0.00694, respectively. e results show that the thrust fluctuation of the ITPMSLM is effectively reduced on the premise of ensuring the best sinusoidal waveform of AGMF and a minimal distortion rate. Figure 18 shows that the air AGMF magnetic density is optimized by taking the angle cutting in the CPMS as a variable. As a result, the thrust fluctuation decreased significantly (by 41.7%), but the average thrust also decreased slightly (by 6.49%). e conclusion is that the application of the optimized structure proposed in this paper should not only greatly reduce the thrust fluctuation but also may address not significantly reducing the average thrust of motor.

New Motor Experiment Platform.
To further verify the effectiveness of this method, the new motor is made, and the dynamic test experiment of thrust fluctuation is carried out. e thrust fluctuation test principle is that in the process of the thrust fluctuation test, the stator, support frame, and pulley of the tested new motor are fixed on the granite platform, and the mover and moving guide rail of the new motor are integrally connected so as to realize high straightness of movement along the static guide rail as the support guide and connect the moving guide rail with the load through the force sensor. e driver gives the motor a one-way movement command (i.e., pulling the load movement). e new motor will pull down the load to make a linear motion under the action of the electromagnetic thrust, and the thrust can be read through the force sensor. erefore, the thrust fluctuation of the motor can be obtained by analyzing the data read by the force sensor. According to the measurement principle of motor thrust fluctuation, the thrust fluctuation test scheme shown in Figure 19 can be obtained.

Shock and Vibration
According to the thrust fluctuation test scheme, a new motor is manufactured, and an experimental platform is built. e experimental platform is composed of a feeding device and a detection unit, as shown in Figure 20. e detection unit includes the magnetic grid ruler and reading head, DYLY-102 force measuring sensor and 24 V DC power supply, DCPCA-090-12-E driver, and driver supporting analysis software and pulley block. Install the force measuring sensor on the auxiliary device, as shown in Figure 21(b). e upper computer controls the driver and adjusts the magnetic grid ruler and the reading head to measure the relative displacement between the mover and the stator. When the motor mover is running, the tooling top force measuring sensor on the workbench measures the motor thrust. To verify the suppression effect of the new motor on thrust fluctuation under different working conditions, the following three groups of experiments are designed: (1) no-load back EMF experimental analysis, (2)     load adaptability experimental analysis, and (3) experimental analysis of speed adaptability.

No-Load Back EMF Test.
ree groups of speeds, v � 0.02 m/s, v � 0.6 m/s, and v � 1 m/s, are tested as shown in Figure 22.
According to the above analysis, the fundamental wave and its higher harmonics are analyzed. When v is 0.02 m/s, 0.6 m/s, and 1 m/s, the no-load back EMF fundamental wave and harmonic of the motor are decomposed to obtain the fundamental wave and harmonic content, respectively, as shown in Figure 23. Figure 23 shows that there are only a small number of fifth harmonics in the no-load back EMF, and the no-load back EMF waveform distortion is 0.20814%, 0.21023%, and 0.21101%. e radial AGMF waveform distribution of the new motor has good sinusoidal property. e measured motor is driven by the control system. e thrust curve is shown in Figure 24.
As shown in Figure Table 5 shows that the thrust fluctuation rates are 0.00918%, 0.00832%, 0.00827%, 0.00811%, and 0.00754%. According to the analytic method, the thrust fluctuation rates are 0.00975%, 0.00930%, 0.00886%, 0.00869%, and 0.00808%. e errors were 5.9%, 10.57%, 6.71%, 6.70%, and 6.69%. e errors are within a reasonable range, and the thrust fluctuation F w obtained according to (9) is less than 0.01%. e experiment verified that when the sinusoidal waveform of the AGMF of the new motor is the best, the thrust fluctuation is quite small. e obtained thrust curve is shown in Figure 23.
As shown in Figure 25, the conclusions that can be drawn from the analysis charts are as follows: (1) In terms of thrust, when the same load of 0. 3 Table 6 shows that the thrust fluctuation rates are 0.00818%, 0.00755%, 0.00601%, 0.00827%, 0.00807%, and 0.00743%. Compared with the analytic method, the errors are 6.68%, 6.71%, 6.69%, 6.71%, 6.72%, and 6.68%, and the thrust fluctuation F w obtained according to (9) is less than 0.01%. erefore, the experiment further verifies that the AGMF composed of CPMS makes 3    the thrust fluctuation of the motor relatively stable at different speeds and that the thrust fluctuation rate is significantly reduced. e CPMS has a good effect on restraining the thrust wave of the motor.

Conclusion
e new motor is designed to reduce thrust fluctuation and improve the driving performance of the motor. e effectiveness of this method is proven by an analytical model build, parameter optimization, and experimental verification. e conclusions are as follows: (1) In this paper, the analytical calculation model of noload magnetic field of the ITPMSLM by the CPMS is derived by using the magnetic charge method, and the analytical formula of radial AGMF density of the no-load magnetic field is given. On this basis, the analytical formulas of the no-load back EMF and thrust are obtained. (2) e new motor is analyzed by the analytical method. When the chamfer of a chamfered permanent magnet is 45 o and h 1 /h 2 � 0.8, the waveform distortion rate of radial AGMF is the smallest, and its sinusoidal property is the best. e finite element comparative analysis is carried out between the new motor and the new ITPMSLM with RPMS of the Halbach array. It is verified that compared with the AGMF composed of a conventional permanent magnet, the CPMS can more effectively improve the sinusoidal waveform of radial AGMF so as to suppress the thrust fluctuation.
(3) e experimental prototype is designed and built, and the new motor under different working conditions is tested. e thrust fluctuation rate F w measured in the experiment is less than 0.01%. is verified that the CPMS can effectively improve the sinusoidal waveform of the AGMF of the ITPMSLM and effectively suppress the thrust fluctuation of the new motor. It provides a method to improve the performance of the ITPMSLM.

Data Availability
e data used to support the findings of this study are included within the article.